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TDA2030A
DESCRIPTION
LINEAR INTEGRATED CIRCUIT
14W HI-FI AUDIO AMPLIFIER
The Contek TDA2030A is a monolithic audio power amplifier integrated circuit.
FEATURES
1
*Very low external component required. *High current output and high operating voltage. *Low harmonic and crossover distortion. *Built-in Over temperature protection. *Short circuit protection between all pins. *Safety Operating Area for output transistors.
TO-220B
PIN CONFIGURATIONS
1 2 3 4 5 Non inverting input Inverting input -VS Output +VS
ABSOLUTE MAXIMUM RATINGS(Ta=25
PARAMETER
Supply Voltage Input Voltage Differential Input Voltage Peak Output Current(internally limited) Total Power Dissipation at Tcase=90 C Storage Temperature Junction Temperature
C)
SYMBOL
Vs Vi Vdi Io Ptot Tstg Tj
VALUE
+-12 Vs +-15 3.5 20 -40~+150 -40~+150
UNIT
V V V A W C C
ELECTRICAL CHARACTERISTICS(Refer to the test circuit, Vs =+-16V,Ta=25
PARAMETER
Supply Voltage Quiescent Drain Current Input Bias Current Input Offset Voltage Input Offset Current
C)
SYMBOL
Vs Id Ib Vos Ios
TEST CONDITIONS
MIN
+-6
TYP
50 0.2 +-2 +-20
MAX
+-22 80 2 +-20 +-200
UNIT
V mA mA mV nA
Vs=+-18v
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1
TDA2030A
(Continued) Output Power Po
LINEAR INTEGRATED CIRCUIT
d=0.5%,Gv=26dB,f=40 to 5kHz RL=8W RL=4W Vs=+-19V, RL=4W Po=15W,RL=4W f=1kHz 15 10 13 18 12 16 100 80 26 0.08 0.03 0.05 0.03 26.5 W W W KHz dB dB % % % %
Power Bandwidth Open loop voltage Gain Closed Loop Voltage Gain Total harmonic distortion
BW Gvo Gvc THD
25.5 Po=0.1 to 14W,RL=4W f=1kHz Po=0.1 to 14W,RL=4W f=1kHz Po=0.1 to 9W,RL=8W f=40 to 15 kHz Po=4W ,RL=8W f2-f1=1 kHz f2=14 kHz,f1=15kHz
Total harmonic Distortion Second Order CCIF Intermodulation distortion Third Order CCIF Intermodulation Distortion Input Noise Voltage Input Noise Voltage Input Noise Current Input Resistance(pin 1) Supply Voltage Rejection Thermal ShutDown Junction Temperature
THD d2
d3
0.08
%
eN iN Ri
B=curve A B= 22Hz to 22kHz B= 22Hz to 22kHz Open loop,f=1kHz RL=4W,Gv=26dB Rg=22kW,f=1kHz
0.5
2 3 80 5 54 145
10 200
mA mV pA MW dB C
Tj
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2
TDA2030A
TEST CIRCUIT
LINEAR INTEGRATED CIRCUIT
+Vs
C5 220 m F C3 100nF
Vi
C1 1 mF R3 22k W
1 Contek TDA2030A
D1 1N4001
5 4 3
R1 13k W D1 1N4001 R4 1W RL
2
R3 680 W C2 22 m F
C6 100 m F
C4 100nF
C7 220nF
-Vs
APPLICATION CIRCUIT
+Vs
C5 220 m F C3 100nF
Vi
C1 1 mF R3 22k W
1 Contek TDA2030A
D1 1N4001
5 4 3
R1 13k W D1 1N4001 R4 1W RL
2
R3 680 W C2 22 m F
C6 100 m F
C4 100nF
C7 220nF
-Vs
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3
TDA2030A
LINEAR INTEGRATED CIRCUIT
+Vs
0.1 mF 220 mF 1N4001
Vi
22 mF
100k W 2.2 mF
100k W
100k W 4.7k W 2.2 mF 1N4001
R4 1W
C7 220nF
Fig.1 Single supply amplifier
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RL=4W
2200 mF
5 Contek 100k W TDA2030A 2 3
1
4
4
TDA2030A
Gv (dB)
140
TYPICAL PERFORMANCE CHARACTERISTICS
Fig.2 Open loop frequency response
Phase
180
LINEAR INTEGRATED CIRCUIT
Fig.3 Output power vs. Supply voltage
Po (W)
24 Gv=26dB d=0.5% f=40 to 15kHz RL=4 W
100
Phase
90
20
60
0
16 RL=8 W 12
Gain
20
-20
8
-60
1 10
2 10
3 10
4 10
Frequency (Hz)
5 10
6 10
7 10
4 24 28 32 36
Vs (V)
40
44
Fig.4 Total harmonic distortion vs. output power
d (%)
2 10
Fig.5 Two tone CCIF intermodulation distortion
d (%)
2 10
Po (W)
1 10
Gv=26dB
1 10
0 10
Vs=38V RL=8 W f=15kHz Vs=32V RL=4 W
0 10
Vs=32V Po=4W RL=4 W Gv=26dB Order (2f1-f2) Order (2f2-f1)
-1 10
-1 10
f=1kHz -2 10 -2 10 -1 10 0 10 1 10
Po (W)
2 10
-2 10
1 10
2 10
3 10
Frequency (Hz)
4 10
5 10
Fig.6 Large signal frequency response
Vo (Vp-p)
30
Fig.7 Maximum allowable power dissipation vs. ambient temperture
Ptot (W)
30
25
Vs=+-15V RL=8 W Vs=+-15V RL=4 W
25
20
20
he a Rt tsin h= k 4 ha X vin he C/ g at W Rth sink =8 hav ing X C/ W
ink ats he e init g inf vin ha /W ink X C ats he ty=25 R
15
15
10
10
5
1 10
2 10
Frequency (kHz)
3 10
4 10
5
-50
0
50
100
Tamb ( X C)
150
200
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TDA2030A
R1 56kW
LINEAR INTEGRATED CIRCUIT
+Vs
C3 0.22 mF
C5 220 mF /40V
Vi
1
R3 Contek 56kW
1N4001
C1 2.2 mF
R6 1.5W
BD908
5
C6 0.22 mF
C2 22 mF
1N4001
R2 56kW
2
TDA2030A 3
R5 30kW R7 1.5W
4
C8 2200 mF
R8 1W
R4 3.3kW C4 10 mF
BD907
C7 0.22 mF
Fig. 8 Single supply high power amplifier( Contek TDA2030+BD908/BD907)
TYPICAL PERFORMANCE OF THE CIRCUIT OF FIG. 8
PARAMETER
Supply Voltage Quiescent Drain Current
SYMBOL
Vs Id
TEST CONDITIONS
Vs=36V d=0.5%,RL=4W f=40Hz to 15kHz,Vs=39V d=0.5%,RL=4W f=40Hz to 15kHz,Vs=36V d=0.5%,f=1kHz, RL=4W Vs=39V d=0.5%,RL=4W f=1kHz,Vs=36V f=1kHz Po=20W,f=1kHz Po=20W,f=40Hz to 15kHz Gv=20dB,Po=20W, f=1kHz,RL=4W RL=4W,Rg=10kW B=curve A,Po=25W RL=4W,Rg=10kW B=curve A,Po=25W
MIN
TYP
36 50 35 28
MAX
44
UNIT
V mA
Output Power
Po
W 44 35 19.5 20 8 0.02 0.05 890 20.5 dB V/msec % % mV
Voltage Gain Slew Rate Total Harmonic Distortion Input Sensitivity
Gv SR d Vi
Signal to Noise Ratio
S/N
108 100
dB
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RL=4W
6
TDA2030A
Po (W) 45
LINEAR INTEGRATED CIRCUIT
Fig. 11 Total harmonic distortion vs. output power
d (%) Vs=36V RL=4 W Gv=20dB
TYPICAL PERFORMANCE CHARACTERISTICS
Fig. 10 Output power vs. supply voltage
35
0 10
25 -1 10 15 f=1kHz 5 -2 10 f=15kHz
24
28
32
34
36
Vs (V)
40
-1 10
0 10
1 10
Po (W)
Fig. 12 Output power vs. Input level
Po (W) 20 Ptot (W) 20
Fig. 13 Power dissipation vs. output power
Gv=26dB
15 15
Complete Amplifier
Gv=20dB
10 10
BD908/ BD907 Contek TDA2030
5
5
0 100 250 400 550 700
Vi (mV)
0 0 8 16 24 32 Po (W)
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TDA2030A
LINEAR INTEGRATED CIRCUIT
+Vs
C5 100 mF C3 100nF D1 1N4001
Vi
C1 1 mF
1
R3 22kW
2
R3 680W C2 22 mF
Contek TDA2030A
5 4 3
R5 C8 R4 1W RL
D2 R1 22kW 1N4001 C6 100 mF C4 C7 100nF 220nF
-Vs
Fig. 14 Typical amplifier with split power supply
Vs+
100 220 C1 mF C6 mF C7 100nF
1 2
Contek TDA2030A
5 4 3
R3 22k W C4 R8 1W
IN
22
mF RL 8W R7 W 22k
R4 W 680
1
R2 22k W
5 3
0.22 mF
R5 22k W C5
Vs22 100 C2 mF C3 100nF
mF
R6 680 W
Fig. 16 Bridge amplifier with split power supply(Po=34W,Vs+=16V,Vs-=16V)
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C9
2
Contek TDA2030A
4
R9 1W
0.22 mF
C8
R1 22k W
8
TDA2030A
LINEAR INTEGRATED CIRCUIT
Multiway loudspeaker systems provide the best possible acoustic performance since each loudspeaker is specially designed and optimized to handle a limited range of frequencies. Commonly, these loudspeaker systems divide the audio spectrum two or three bands. To maintain a flat frequency response over the Hi-Fi audio range the bands cobered by each loudspeaker must overlap slightly. Imbalance between the loudspeakers produces unacceptable results therefore it is important to ensure that each unit generates the correct amount of acoustic energy for its segments of the audio spectrum. In this respect it is also important to know the energy distribution of the music spectrum to determine the cutoff frequencies of the crossover filters(see Fig. 18).As an example,1 100W three-way system with crossover frequencies of 400Hz and 3khz would require 50W for the woofer,35W for the midrange unit and 15W for the tweeter. Both active and passive filters can be used for crossovers but active filters cost significantly less than a good passive filter using aircored inductors and non-electrolytic capacitors. In addition active filters do not suffer from the typical defects of passive filters: --Power less; --Increased impedance seen by the loudspeaker(lower damping) --Difficulty of precise design due to variable loudspeaker impedance. Obviously, active crossovers can only be used if a power amplifier is provide for each drive unit. This makes it particularly interesting and economically sound to use monolithic power amplifiers. In some applications complex filters are not relay necessary and simple RC low-pass and high-pass networks(6dB/octave) can be recommended. The result obtained are excellent because this is the best type of audio filter and the only one free from phase and transient distortion. The rather poor out of band attenuation of single RC filters means that the loudspeaker must operate linearly well beyond the crossover frequency to avoid distortion. A more effective solution, named "Active power Filter" by SGS is shown in Fig. 19. The proposed circuit can realize combined power amplifiers and 12dB/octave or 18dB octave high-pass or lowpass filters. In proactive, at the input pins amplifier two equal and in-phase voltages are available, as required for the active filter operations. The impedance at the Pin(-) is of the order of 100 W,while that of the Pin (+) is very high, which is also what was wanted.
Fig. 18 Power distribution vs. frequency
100 IEC/DIN NOISE SPECTRUM FOR SPEAKER TESTING
MULTIWAY SPEAKER SYSTEMS AND ACTIVE BOXES
Fig. 19 Active power filter
80
C1 C2 C3
Morden Music Spectrum
Vs+ RL
60
R1 R2
R3 Vs-
3.3kW
40
20
100W
0
1 10
2 10
3 10
4 10
5 10
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TDA2030A
LINEAR INTEGRATED CIRCUIT
The components values calculated for fc=900Hz using a Bessel 3rd Sallen and Key structure are: C1=C2=C3=22nF,R1=8.2K W,R2=5.6KW,R3=33KW. Using this type of crossover filter, a complete 3-way 60W active loudspeaker system is shown in Fig. 20. It employs 2nd order Buttherworth filter with the crossover frequencies equal to 300Hz and 3kHz. The midrange section consistors of two filters a high pass circuit followed by a low pass network. With Vs=36V the output power delivered to the woofer is 25W at d=0.06%( 30W at d=0.5%).The power delivered to the midrange and the tweeter can be optimized in the design phase taking in account the loudspeaker efficiency and impedance(RL=4 W to 8W). It is quite common that midrange and tweeter speakers have an efficiency 3dB higher than woofers.
Vs+
0.22 mF
Low-pass 300Hz
IN
680W
1 mF 22k W 22k W
2200 mF
1
18nF
5
0.22 mF
1N4001
1.5W
BD908
33nF
2
Contek TDA2030A
4
2200 mF
22kW
3.3kW
1N4001
0.22 mF
100W
1.5W
Woofer Band-pass 300Hz to 3kHz
0.1 mF 0.1 mF 22k W 22k W
Vs+
0.22 mF 1N4001
1
18nF
5
Contek TDA2030A
3.3kW
6.8kW
4
1W 0.22 mF
220 mF
3.3nF
2
1N4001 100 mF 2.2k W
Midrange
100W
Vs+
0.22 mF 1N4001
Vs+
High-pass 3kHz
0.1 mF 0.1 mF
1
22kW
5
Contek TDA2030A
22kW
12kW
4
1W
1N4001
100 mF
2
100 mF
22kW
47 mF
2.2k W
0.22 mF
High-pass 3kHz
Tweeter
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100W
8W
3
8W
3
4W
BD907
1W
100 mF
3
10
TDA2030A
LINEAR INTEGRATED CIRCUIT
MUSICAL INSTRUMENTS AMPLIFIERS
Another important field of application for active system is music. In this area the use of several medium power amplifiers is more convenient than a single high power amplifier, and it is also more reliable. A typical example(see Fig. 21) consist of four amplifiers each driving a low-cost, 12 inch loudspeaker. This application can supply 80 to 160W rms.
TRANSIENT INTER-MODULATION DISTORTION(TIM)
Transient inter-modulation distortion is an unfortunate phenomena associated with negative-feedback amplifiers. When a feedback amplifier receives an input signal which rises very steeply, i.e. contains high-frequency components, the feedback can arrive too late so that the amplifiers overloads and a burst of inter-modulation distortion will be produced as in Fig.22.Since transients occur frequently in music this obviously a problem for the designed of audio amplifiers. Unfortunately, heavy negative feedback is frequency used to reduce the total harmonic distortion of an amplifier, which tends to aggravate the transient inter- modulation(TIM situation.)The best known
Fig.21 High power active box for musical instrument 20 to 40W Amplifier
Fig.22 Overshoot phenomenon in feedback amplifiers
FEEDBACK PATH
V4 INPUT V1
20 to 40W Amplifier
PRE AMPLIFIER
V2
V3
POWER AMPLIFIER
OUTPUT V4
V1
20 to 40W Amplifier
V2
20 to 40W Amplifier
V3 V4
method for the measurement of TIM consists of feeding sine waves superimposed onto square wavers, into the amplifier under test. The output spectrum is then examined using a spectrum analyzer and compared to the input. This method suffers from serious disadvantages: the accuracy is limited, the measurement is a tatter delicate operation and an expensive spectrum analyzer is essential. A new approach (see Technical Note 143(Applied by SGS to monolithic amplifiers measurement is fast cheap, it requires nothing more sophisticated than an oscilloscope-and sensitive-and it can be used down to the values as low as 0.002% in high power amplifiers. The "inverting- sawtooth" method of measurement is based on the response of an amplifier to a 20KHz saw-tooth wave-form. The amplifier has no difficulty following the slow ramp but it cannot follow the fast edge. The output will follow the upper line in Fig.23 cutting of the shade area and thus increasing the mean level. If this output signal is filtered to remove the saw-tooth, direct voltage remains which indicates the amount of TIM distortion, although it is difficult to measure because it is indistinguishable from the DC offset of the amplifier. This problem is neatly avoided in the IS-TIM method by periodically inverting the saw-tooth wave-form at a low audio frequency as shown in Fig.24.Inthe case of the saw-tooth in Fig. 25 the means level was increased by the TIM distortion, for a saw-tooth in the other direction the opposite is true.
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TDA2030A
SR(V/ s) m
m2 m1
LINEAR INTEGRATED CIRCUIT
Input Signal Filtered Output Siganal
Fig.23 20kHz sawtooth waveform
Fig.24 Inverting
sawtooth waveform
The result is an AC signal at the output whole peak-to-peak value is the TIM voltage, which can be measured easily with an oscilloscope. If the peak- topeak value of the signal and the peak-to-peak of the inverting sawtooth are measured, the TIM can be found very simply from:
TIM =
VOUT Vsawtooth
* 100
1 10
Fig. 25 TIM distortion Vs. Output Power SR(V/
2 10
Fig. 26 TIM design diagram(fc=30kHz)
TIM(%)
0 10
TDA2030A BD908/907 Gv=26dB Vs=36V RL=4W
s)
RC Filter fc=30kHz
1 10
-1 10
RC Filter fc=30kHz
0 10
-2 10
-1 10
0 10
1 10
Po(W)
2 10
-1 10
-1 10
TI M =0 .0 TI 1% M =0 .1 TI % M =1 %
0 10
1 10
Vo(Vp-p)
2 10
In Fig.25 The experimental results are shown for the 30W amplifier using the TDA2030A as a driver and a low-cost complementary pair. A simple RC filter on the input of the amplifier to limit the maximum signal slope(SS) is an effective way to reduce TIM. The Diagram of Fig.26 originated by SGS can be used to find the Slew- Rate(SR) required for a given output power or voltage and a TIM design target. For example if an anti-TIM filter with a cutoff at 30kHz is used and the max. Peak to peak output voltage is 20V then, referring to the diagram, a Slew-Rate of 6V/ ms is necessary for 0.1% TIM. As shown Slew-Rates of above 10V/ ms do not contribute to a further reduction in TIM. Slew-Rates of 100V/ms are not only useless but also a disadvantage in hi-fi audio amplifiers because they tend to turn the amplifier into a radio receiver.
POWER SUPPLY
Using monolithic audio amplifier with non regulated supply correctly. In any working case it must provide a supply voltage less than the maximum value fixed by the IC breakdown voltage.
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TDA2030A
LINEAR INTEGRATED CIRCUIT
It is essential to take into account all the working conditions, in particular mains fluctuations and supply voltage variations with and without load. The TDA2030(Vsmax=44V) is particularly suitable for substitution of the standard IC power amplifiers(with Vsmax=36V) for more reliable applications. An example, using a simple full-wave rectifier followed by a capacitor filter, is shown in the table and in the diagram of Fig.27. A regulated supply is not usually used for the power output stages because of its dimensioning must be done taking into account the power to supply in signal peaks. They are not only a small percentage of the total music signal, with consequently large overdimensioning of the circuit. Even if with a regulated supply higher output power can be obtained(Vs is constant in all working conditions),the additional cost and power dissipation do not usually justify its use. using non-regulated supplies, there are fewer designee restriction. In fact, when signal peaks are present, the capacitor filter acts as a flywheel supplying the required energy.
In average conditions, the continuous power supplied is lower. The music power/continuous power ratio is greater in case than for the case of regulated supplied, with space saving and cost reduction.
Fig.27 DC characteristics of 50W non-regulated supply Vo(V)
36
Ripple (Vp-p)
34 Ripple 32 2 30 4
220V
3300 mF
Vo
Vout
28
0
0
0.4
0.8
1.2
1.6
2.0
Io(A)
Mains(220V)
+20% +15% +10% -10% -15% -20%
Secondary Voltage
28.8V 27.6V 26.4V 24V 21.6V 20.4V 19.2V Io=0 43.2V 41.4V 39.6V 36.2V 32.4V 30.6V 28.8V
DC Output Voltage(Vo)
Io=0.1A 42V 40.3V 38.5V 35V 31.5V 29.8V 28V Io=1A 37.5V 35.8V 34.2V 31V 27.8V 26V 24.3
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TDA2030A
LINEAR INTEGRATED CIRCUIT
SHORT CIRCUIT PROTECTION
The Contek TDA2030 has an original circuit which limits the current of the output transistors. This function can be considered as being peak power limiting rather than simple current limiting. It reduces the possibility that the device gets damaged during an accidental short circuit from AC output to Ground.
THERMAL SHUT-DOWN
The presence of a thermal limiting circuit offers the following advantages: 1).An overload on the output (even if it is permanent),or an above limit ambient temperature can be easily supported since the Tj can not be higher than 150 C 2).The heatsink can have a smaller factor of safety compared with that of a congenital circuit, There is no possibility of device damage due to high junction temperature increase up to 150, the thermal shut-down simply reduces the power dissipation and the current consumption.
APPLICATION SUGGESTION
The recommended values of the components are those shown on application circuit of Fig.14. Different values can be used. The following table can help the designer.
COMPONENT
RECOMMENDED VALUE
22KW 680W 22KW 1W
PURPOSE
LARGE THAN RECOMMENDED VALUE
Increase of Gain Decrease of Gain Increase of input impedance Danger of oscillation at high frequencies with inductive loads. Poor high frequencies attenuation
LARGE THAN RECOMMENDED VALUE
Decrease of Gain Increase of Gain Decrease of input impedance
R1 R2 R3 R4
Closed loop gaon setting. Closed loop gaon setting. Non inverting input biasing Frequency stacility
R5 C1 C2 C3,C4 C5,C6 C7 C8 D1,D2
3R2 1mF 22mF 0.1mF 100mF 0.22mF 1/(2p*B*R1) 1N4001
Upper frequency cutoff Input DC decoupling Inverting DC decoupling Supply voltage bypass Supply voltage bypass Frequency stability Upper frequency cutoff To protect the device against output voltage spikes.
Dange of oscillation Increase of low frequencies cutoff Increase of low frequencies cutoff Dange of oscillation Dange of oscillation Larger bandwidth Larger bandwidth
smaller bandwidth
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