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TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
D D D D D D D D D D D D D
Compatible With PC 99 Desktop Line-Out Into 10-k Load Compatible With PC 99 Portable Into 8- Load Internal Gain Control, Which Eliminates External Gain-Setting Resistors DC Volume and Gain Control Adjustable From 34 dB to - 86 dB Bass Boost Buffered Docking Station Outputs 2-W/Ch Output Power Into 3- Load PC-Beep Input Depop Circuitry Stereo Input MUX Fully Differential Input Low Supply Current and Shutdown Current Surface-Mount Power Packaging 28-Pin TSSOP PowerPADTM
PWP PACKAGE (TOP VIEW)
GND LOUT+ BBENABLE BYPASS LIN LHPIN LLINEIN PC-BEEP RLINEIN RHPIN RIN SHUTDOWN HP/LINE ROUT+
1 2 3 4 5 6 7 8 9 10 11 12 13 14
28 27 26 25 24 23 22 21 20 19 18 17 16 15
LOUT- CLK LDOCKOUT PVDD BUFFGAIN VOLUME VDD BBIN BBOUT PVDD RDOCKOUT SE/BTL ROUT- GND
description
The TPA6010A4 is a stereo audio power amplifier in a 28-pin TSSOP thermally enhanced package capable of delivering 2 W of continuous RMS output power into 3- loads. When driving 1 W into 8- speakers, the TPA6010A4 has less than 0.22% THD+N across its specified frequency range. The TPA6010A4 has several features optimized for notebook PCs including bass boost, docking station outputs, dc volume control, and dc gain control. The TPA6010A4 has buffer and volume control gain stages that are set by dc voltages. The buffer has differential input and differential output. The gain of the buffer, which is controlled by the dc voltage on the BUFFGAIN terminal, is adjustable from - 46 dB to 14 dB. The docking station output is 6 dB lower than the buffer gain because the buffer has a differential output and the docking station output is taken from just one of the buffer outputs. The volume control amplifier is adjustable from - 34 dB to 20 dB in the BTL mode and is 6 dB lower in the SE mode. The volume control stage is adjustable by dc voltage on the VOLUME terminal. The amplifier gain from input-to-speaker is the sum of the volume control and the buffer gain. The input-to-speaker gain is adjustable from - 86 dB to 34 dB in the BTL mode and - 92 dB to 28 dB in the SE mode. The bass boost of the amplifier sums the right and left inputs, adds gain, filters out the high frequencies, and then adds the bass boost signal back into the output power amplifier. The frequency of the bass boost is adjusted by adding an RC filter from BBOUT to BBIN. The gain of the bass boost is set to 12 dB if the same bass is present in both the right and left channels. If the bass is present in just one of the channels, the gain of the bass is set to 9.5 dB. The gain can be reduced by adding a voltage divider from BBIN to BBOUT. If not using the bass boost, pull the BBENABLE pin low.
Please be aware that an important notice concerning availability, standard warranty, and use in critical applications of Texas Instruments semiconductor products and disclaimers thereto appears at the end of this data sheet.
PowerPAD is a trademark of Texas Instruments.
PRODUCTION DATA information is current as of publication date. Products conform to specifications per the terms of Texas Instruments standard warranty. Production processing does not necessarily include testing of all parameters.
Copyright (c) 2000, Texas Instruments Incorporated
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TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
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The PowerPADTM package (PWP) delivers a level of thermal performance that was previously achievable only in TO-220-type packages. Thermal impedances of approximately 35C/W are truly realized in multilayer PCB applications. This allows the TPA6010A4 to operate at full power into 8- loads at ambient temperatures of 85C.
functional block diagram
BUFFGAIN RHPIN RLINEIN RIN R MUX - +
VOLUME - +
RDOCKOUT
- ROUT+ +
-
BUFFGAIN VOLUME CLK DC GAIN and Volume Control
+
ROUT-
PVDD VDD BYPASS SHUTDOWN GND
Power Management
- + Bass Boost
BBOUT
-
RBB
PC-BEEP
PC BEEP
+
BBIN CBB
SE/BTL HP/LINE
MUX CONTROL
BBENABLE
LHPIN LLINEIN LIN
L MUX
- + BUFFGAIN
- + VOLUME
- + LOUT+
-
LOUT- + LDOCKOUT
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TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
AVAILABLE OPTIONS TA PACKAGED DEVICE TSSOP (PWP)
- 40C to 85C TPA6010A4PWP The PWP package is available taped and reeled. To order a taped and reeled part, add the suffix R to the part number (e.g., TPA6010A4PWPR).
Terminal Functions
TERMINAL NAME BBENABLE BBIN BBOUT BYPASS CLK BUFFGAIN GND HP/LINE LHPIN LIN LLINEIN LDOCKOUT LOUT+ LOUT- PC-BEEP PVDD RHPIN RIN RLINEIN RDOCKOUT ROUT+ ROUT- SE/BTL SHUTDOWN VDD VOLUME NO. 3 21 20 4 27 24 1, 15 13 6 5 7 26 2 28 8 19, 25 10 11 9 18 14 16 17 12 22 23 I I I I O O O I I I I I O O O I I I I I I I/O I I O DESCRIPTION Bass boost circuitry is active when high. Bass boost circuitry is shut down when low. BBIN is the buffered input to the power amplifier from the bass boost circuitry. BBOUT is the bass boost output. A low pass filter must be placed from BBOUT to BBIN to select the low frequencies to be boosted. Tap to voltage divider for internal midsupply bias generator If a 47-nF capacitor is attached, the TPA6010A4 generates an internal clock. An external clock can override the internal clock input to this terminal. The gain of the dockout buffer is adjustable from - 52dB to 8 dB to LDOCKOUT and RDOCKOUT, and is set by a dc voltage from 0 V to 3.54 V. When the dc level is over 3.54 V, the device is muted. Ground connection for circuitry. Connected to thermal pad. MUX control input, hold high to select LHPIN or RHPIN, hold low to select LLINEIN or RLINEIN. Left channel headphone input, selected when HP/LINE is held high Common left input for fully differential input. AC ground for single-ended inputs Left channel line negative input, selected when HP/LINE is held low LDOCKOUT is the buffered output of LLINEIN or LHPIN. Left channel positive output in BTL mode and positive output in SE mode Left channel negative output in BTL mode and high-impedance in SE mode The input for PC Beep mode. PC-BEEP is enabled when a > 1-V (peak-to-peak) square wave is input to PC-BEEP. Power supply for output stage Right channel headphone input, selected when HP/LINE is held high Common right input for fully differential input. AC ground for single-ended inputs Right channel line input, selected when HP/LINE is held low RDOCKOUT is the buffered output of RLINEIN or RHPIN. Right channel positive output in BTL mode and positive output in SE mode Right channel negative output in BTL mode and high-impedance in SE mode Input MUX control input. When this terminal is held high, the LHPIN or RHPIN and SE output is selected. When this terminal is held low, the LLINEIN or RLINEIN and BTL output are selected. When held low, this terminal places the entire device, except PC-BEEP detect circuitry, in shutdown mode. Analog VDD input supply. This terminal needs to be isolated from PVDD to achieve highest performance. VOLUME detects the dc level at the terminal and sets the gain for 31 discrete steps covering a range of 20 dB to - 40 dB for dc levels of 0.15 V to 3.54. When the dc level is over 3.54 V, the device is muted.
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TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
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absolute maximum ratings over operating free-air temperature range (unless otherwise noted)
Supply voltage, VDD . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 6 V Input voltage, VI . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 0.3 V to VDD +0.3 V Continuous total power dissipation . . . . . . . . . . . . . . . . . . . . . internally limited (see Dissipation Rating Table) Operating free-air temperature range, TA . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 40C to 85C Operating junction temperature range, TJ . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 40C to 150C Storage temperature range, Tstg . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . - 65C to 150C Lead temperature 1,6 mm (1/16 inch) from case for 10 seconds . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 260C
Stresses beyond those listed under "absolute maximum ratings" may cause permanent damage to the device. These are stress ratings only, and functional operation of the device at these or any other conditions beyond those indicated under "recommended operating conditions" is not implied. Exposure to absolute-maximum-rated conditions for extended periods may affect device reliability. DISSIPATION RATING TABLE PACKAGE PWP TA 25C 2.7 W DERATING FACTOR 21.8 mW/C TA = 70C 1.7 W TA = 85C 1.4 W
Please see the Texas Instruments document, PowerPAD Thermally Enhanced Package Application Report (literature number SLMA002), for more information on the PowerPADTM package. The thermal data was measured on a PCB layout based on the information in the section entitled Texas Instruments Recommended Board for PowerPAD on page 33 of the before mentioned document.
recommended operating conditions
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Supply voltage, VDD 4.5 4 2 5.5 V V V C High-level High level input voltage, VIH voltage Low-level Low level input voltage VIL voltage, Operating free-air temperature, TA SE/BTL, HP/LINE SE/BTL, HP/LINE SHUTDOWN, BBENABLE SHUTDOWN, BBENABLE - 40 3 0.8 85
MIN
MAX
UNIT
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operating characteristics, VDD = 5 V, TA = 25C, RL = 8 , Gain = 6 dB, BTL mode (unless otherwise noted)
Vn kSVR BOM PO THD + N Vn Supply ripple rejection ratio Bandwidth, maximum output power Total harmonic distortion plus noise Output power Output noise voltage Output noise voltage PARAMETER CB = 1 F, f = 20 Hz to 20 kHz f = 1 kHz, , CB = 1 F PO = 1 W, THD = 0.5% THD = 0.06%, CB = 1 F, f = 20 Hz to 20 kHz TEST CONDITIONS SE mode BTL mode SE mode BTL mode f = 20 Hz to 15 kHz f = 1 kHz SE mode BTL mode MIN 0.4% TYP >15 32 50 50 56 32 50 1 MAX VRMS VRMS UNIT kHz dB W
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electrical characteristics at specified free-air temperature, VDD = 5 V, TA = 25C (unless otherwise noted) operating characteristics, VDD = 5 V, TA = 25C, RL = 4 , Gain = 6 dB, BTL mode (unless otherwise noted)
kSVR BOM PO THD + N IDD(SD) IDD |IIL| |IIH| PSRR |VOS| Supply current shutdowm mode current, Supply current Low-level input current High-level input current Power supply rejection ratio Output offset voltage (measured differentially) Supply ripple rejection ratio Bandwidth, maximum output power Total harmonic distortion plus noise Output power PARAMETER PARAMETER f = 1 kHz, , CB = 1 F PO = 1 W, THD = 3% THD = 0.5%,
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TEST CONDITIONS
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SE mode BTL mode f = 20 Hz to 15 kHz f = 1 kHz PC-BEEP = 0 V PC-BEEP = 2.5 V SE mode BTL mode VDD = 5.5 V, VI = 0 V VDD = 4.9 V to 5.1 V VDD = 5.5 V, VI = VDD TEST CONDITIONS MIN MIN 0.45% TYP TYP >15 40 50 6.5 62 95 12 67 2 MAX MAX 200 250 10 18 25 1 1 UNIT UNIT kHz dB mA mV W A A A dB
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APPLICATION INFORMATION
Table 1. Internal Buffer Gain and Volume Gain
INTERNAL BUFFER GAIN BUFFGAIN (Terminal 24) FROM (V) 0 0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3 3.1 3.2 3.3 3.4 3.5 TO (V) 0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3 3.1 3.2 3.3 3.4 3.5 5 INTERNAL GAIN (dB) 14 12 10 8 6 4 2 0 -2 -4 -6 -8 - 10 - 12 - 14 - 16 - 18 - 20 - 22 - 24 - 26 - 28 - 30 - 32 - 34 - 36 - 38 - 40 - 42 - 44 - 46 mute DOCKOUT GAIN (dB) 8 6 4 2 0 -2 -4 -6 -8 - 10 - 12 - 14 - 16 - 18 - 20 - 22 - 24 - 26 - 28 - 30 - 32 - 34 - 36 - 38 - 40 - 42 - 44 - 46 - 48 - 50 - 52 mute FROM (V) 0 0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.3 1.4 1.5 1.6 17 1.8 1.9 2 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3 3.1 3.2 3.3 3.4 3.5 TO (V) 0.5 0.6 0.7 0.8 0.9 1 1.1 1.2 1.3 1.4 1.5 1.6 1.7 1.8 1.9 2 2.1 2.2 2.3 2.4 2.5 2.6 2.7 2.8 2.9 3 3.1 3.2 3.3 3.4 3.5 5 VOLUME GAIN VOLUME (Terminal 23) BTL GAIN (dB) 20 18 16 14 12 10 8 6 4 2 0 -2 -4 -6 -8 - 10 - 12 - 14 - 16 - 18 - 20 - 22 - 24 - 26 - 28 - 30 - 32 - 34 - 36 - 38 - 40 mute SE GAIN (dB) 14 12 10 8 6 4 2 0 -2 -4 -6 -8 - 10 - 12 - 14 - 16 - 18 - 20 - 22 - 24 - 26 - 28 - 30 - 32 - 34 - 36 - 38 - 40 - 42 - 44 - 46 mute
NOTE: The overall input-to-speaker gain is the sum of the internal buffer gain and volume gain found in Table 1. Therefore, the total input-to-speaker gain ranges between -86 dB and 34 dB in the BTL mode and between -92 dB and 28 dB in the SE mode.
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SLOS268 - JUNE 2000
APPLICATION INFORMATION
Right Headphone Input Signal Right Line Input Signal CRHP 0.47 F RDOCKOUT CRLINE 0.47 F CRIN 0.47 F 10 9 11 RHPIN RLINEIN RIN R MUX BUFFGAIN - + VOLUME - + 18
- +
ROUT+ 14
To Right Docking Station Input See Note B
VDD 50 k
- 24 23 27 CCLK 47 nF BUFFGAIN VOLUME CLK DC GAIN and Volume Control
ROUT- 16
+ VDD 100 k
COUTR 330 F 1 k
VDD 50 k VDD See Note A CSR 0.1 F VDD CSR 0.1 F To System Control PC Beep Input Signal CPCB 0.47 F CLHP 0.47 F CLLINE 0.47 F CBYP 0.47 F
19, 25 PVDD 22 VDD 4 BYPASS 12 SHUTDOWN 1, 15 GND
Power Management Depop Circuitry
- +
BBOUT 20 Bass Boost RBB -
8
PC-BEEP
PC BEEP
+
BBIN
21
1 k COUTL 330 F To System Control
CBB BBENABLE 3
17 13 6 7 5
SE/BTL HP/LINE LHPIN LLINEIN LIN
MUX CONTROL L MUX
Left Headphone Input Signal Left Line Input Signal
- + BUFFGAIN
- + VOLUME
- +
LOUT+ 2
CLIN 0.47 F
-
LOUT- 28
+ LDOCKOUT 26 100 k To Left Docking Station Input See Note B
A 0.1 F ceramic capacitor should be placed as close as possible to the IC. For filtering lower-frequency noise signals, a larger electrolytic capacitor of 10 F or greater should be placed near the audio power amplifier. NOTE B: A DC-blocking capacitor should be placed at each input to the amplifier in the docking station, as the RDOCKOUT and LDOCKOUT pins are biased to VDD/2. NOTE A:
Figure 1. Typical TPA6010A4 Application Circuit Using Single-Ended Inputs and Input MUX
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APPLICATION INFORMATION
N/C Right Negative Differential Input Signal Right Positive Differential Input Signal CRIN- 0.47 F CRIN+ 0.47 F VDD 50 k 10 RHPIN 9 RLINEIN 11 RIN R MUX BUFFGAIN - + VOLUME - + RDOCKOUT 18 To Right Docking Station Input See Note B
- +
ROUT+ 14
- 24 BUFFGAIN 23 VOLUME 27 CLK CCLK 47 nF DC GAIN and Volume Control
ROUT- 16
+ VDD 100 k
COUTR 330 F 1 k
VDD 50 k See Note A CSR 0.1 F CSR 0.1 F To System Control PC Beep Input Signal N/C Left Negative Differential Input Signal Left Positive Differential Input Signal CLIN- 0.47 F CLIN+ 0.47 F CPCB 0.47 F CBYP 0.47 F
VDD
VDD
19, 25 22 4 12 1, 15
PVDD VDD BYPASS SHUTDOWN GND
Power Management Depop Circuitry
- +
BBOUT Bass Boost
20
RBB -
8 PC-BEEP
+ PC BEEP
BBIN
21
1 k COUTL 330 F To System Control
CBB BBENABLE 3
17 SE/BTL 13 HP/LINE 6 LHPIN 7 LLINEIN 5 LIN
MUX CONTROL L MUX
- + BUFFGAIN
- + VOLUME
- +
LOUT+ 2
-
LOUT- 28
+ LDOCKOUT 26 100 k To Left Docking Station Input See Note B
A 0.1 F ceramic capacitor should be placed as close as possible to the IC. For filtering lower-frequency noise signals, a larger electrolytic capacitor of 10 F or greater should be placed near the audio power amplifier. NOTE B: A DC-blocking capacitor should be placed at each input to the amplifier in the docking station, as the RDOCKOUT and LDOCKOUT pins are biased to VDD/2. NOTE A:
Figure 2. Typical TPA6010A4 Application Circuit Using Differential Inputs
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APPLICATION INFORMATION input resistance
Each gain setting is achieved by varying the input resistance of the amplifier, which can range from its smallest value to over 6 times that value. As a result, if a single capacitor is used in the input high pass filter, the -3 dB or cut-off frequency will also change by over 6 times. If an additional resistor is connected from the input pin of the amplifier to ground, as shown in the figure below, the variation of the cut-off frequency will be much reduced.
RF C Input Signal R IN RI
Figure 3. Resistor on Input for Cut-Off Frequency The input resistance at each gain setting is given in Figure 3. The -3 dB frequency can be calculated using the following formula:
f -3 dB
+
1
2p C R R
o
I
(1)
If the filter must be more accurate, the value of the capacitor should be increased while value of the resistor to ground should be decreased. In addition, the order of the filter could be increased.
input capacitor, CI
In the typical application an input capacitor, CI, is required to allow the amplifier to bias the input signal to the proper dc level for optimum operation. In this case, CI and the input impedance of the amplifier, ZI, form a high-pass filter with the corner frequency determined in equation 2.
-3 dB
fc
1 + 2 pZ C
(2)
II
fc
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APPLICATION INFORMATION input capacitor, CI (continued)
The value of CI is important to consider as it directly affects the bass (low frequency) performance of the circuit. Consider the example where ZI is 710 k and the specification calls for a flat bass response down to 40 Hz. Equation 2 is reconfigured as equation 3.
CI 1 + 2 pZ fc
I
(3)
In this example, CI is 5.6 nF so one would likely choose a value in the range of 5.6 nF to 1 F. A further consideration for this capacitor is the leakage path from the input source through the input network (CI) and the feedback network to the load. This leakage current creates a dc offset voltage at the input to the amplifier that reduces useful headroom, especially in high gain applications. For this reason a low-leakage tantalum or ceramic capacitor is the best choice. When polarized capacitors are used, the positive side of the capacitor should face the amplifier input in most applications as the dc level there is held at VDD/2, which is likely higher than the source dc level. Note that it is important to confirm the capacitor polarity in the application. power supply decoupling, CS The TPA6010A4 is a high-performance CMOS audio amplifier that requires adequate power supply decoupling to ensure the output total harmonic distortion (THD) is as low as possible. Power supply decoupling also prevents oscillations for long lead lengths between the amplifier and the speaker. The optimum decoupling is achieved by using two capacitors of different types that target different types of noise on the power supply leads. For higher frequency transients, spikes, or digital hash on the line, a good low equivalent-series-resistance (ESR) ceramic capacitor, typically 0.1 F placed as close as possible to the device VDD lead works best. For filtering lower-frequency noise signals, a larger aluminum electrolytic capacitor of 10 F or greater placed near the audio power amplifier is recommended. midrail bypass capacitor, CBYP The midrail bypass capacitor, CBYP, is the most critical capacitor and serves several important functions. During startup or recovery from shutdown mode, CBYP determines the rate at which the amplifier starts up. The second function is to reduce noise produced by the power supply caused by coupling into the output drive signal. This noise is from the midrail generation circuit internal to the amplifier, which appears as degraded PSRR and THD+N. Bypass capacitor, CBYP, values of 0.47 F to 1 F ceramic or tantalum low-ESR capacitors are recommended for the best THD and noise performance.
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TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
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APPLICATION INFORMATION
bass boost operation The bass boost feature of the TPA6010A4 sums the left and right inputs, adds gain, filters out the high frequencies, and adds the bass-boosted signal back into the current-gain stage of the amplifier. The cutoff frequency is set by RBB and CBB as shown in equation 4.
-3 dB
fc
+ 2 pR 1 C
(4)
BB BB
fc
The gain of the bass boost is set internally at 12 dB if bass is present in both the right and left channels. If bass is only present in one of the channels, the boost is reduced to 9.5 dB. The bass boost gain may also be reduced by adding an L-pad voltage divider between the RBB-CBB filter and the BBIN pin. An example circuit is shown in figure 4.
RBB BBOUT CBB R1 BBIN R2
Figure 4. L-Pad Voltage Divider Circuit The total bass boost gain may be determined by using equation 5.
Bass Boost Gain
+ 12 dB ) 20Log + 9.5 dB ) 20Log
R2 R1
) R2
R2
(bass present on both channels) (5) (bass present on only one channel)
Bass Boost Gain
R1
) R2
Consider the following example application. The desired cutoff frequency for the bass boost is 300 Hz and the desired bass boost gain is 6 dB. The filter components could be RBB = 1.1 k and CBB = 0.47 F, while the L-pad components could be R1 = R2 = 10 k. If the bass boost feature is not to be used or if the user wishes to disable the boost, the BBENABLE pin should be pulled low. Finally, as illustrated in the functional block diagram, the bass boost is only applied to the speaker outputs, not to the docking station outputs.
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TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
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APPLICATION INFORMATION output coupling capacitor, CC
In the typical single-supply SE configuration, an output coupling capacitor (CC) is required to block the dc bias at the output of the amplifier thus preventing dc currents in the load. As with the input coupling capacitor, the output coupling capacitor and impedance of the load form a high-pass filter governed by equation 6.
-3 dB
fc
+ 2 pR1 C
LC
(6)
fc
The main disadvantage, from a performance standpoint, is the load impedances are typically small, which drives the low-frequency corner higher degrading the bass response. Large values of CC are required to pass low frequencies into the load. Consider the example where a CC of 330 F is chosen and loads vary from 3 , 4 , 8 , 32 , 10 k, and 47 k. Table 2 summarizes the frequency response characteristics of each configuration. Table 2. Common Load Impedances vs Low Frequency Output Characteristics in SE Mode
RL 3 4 8 32 10,000 47,000 CC 330 F 330 F 330 F 330 F 330 F 330 F LOWEST FREQUENCY 161 Hz 120 Hz 60 Hz 15 Hz 0.05 Hz 0.01 Hz
As Table 2 indicates, most of the bass response is attenuated into a 4- load, an 8- load is adequate, headphone response is good, and drive into line level inputs (a home stereo for example) is exceptional.
using low-ESR capacitors
Low-ESR capacitors are recommended throughout this applications section. A real (as opposed to ideal) capacitor can be modeled simply as a resistor in series with an ideal capacitor. The voltage drop across this resistor minimizes the beneficial effects of the capacitor in the circuit. The lower the equivalent value of this resistance the more the real capacitor behaves like an ideal capacitor.
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APPLICATION INFORMATION bridged-tied load versus single-ended mode
Figure 5 shows a Class-AB audio power amplifier (APA) in a BTL configuration. The TPA6010A4 BTL amplifier consists of two Class-AB amplifiers driving both ends of the load. There are several potential benefits to this differential drive configuration but initially consider power to the load. The differential drive to the speaker means that as one side is slewing up, the other side is slewing down, and vice versa. This in effect doubles the voltage swing on the load as compared to a ground referenced load. Plugging 2 x VO(PP) into the power equation, where voltage is squared, yields 4x the output power from the same supply rail and load impedance (see equation 7).
V (rms)
+ +
V O(PP)
22 2
(7)
Power
V (rms) RL
VDD
VO(PP)
RL VDD
2x VO(PP)
-VO(PP)
Figure 5. Bridge-Tied Load Configuration
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TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION
In a typical computer sound channel operating at 5 V, bridging raises the power into an 8- speaker from a singled-ended (SE, ground reference) limit of 250 mW to 1 W. In sound power that is a 6-dB improvement -- which is loudness that can be heard. In addition to increased power there are frequency response concerns. Consider the single-supply SE configuration shown in Figure 6. A coupling capacitor is required to block the dc offset voltage from reaching the load. These capacitors can be quite large (approximately 33 F to 1000 F) so they tend to be expensive, heavy, occupy valuable PCB area, and have the additional drawback of limiting low-frequency performance of the system. This frequency limiting effect is due to the high pass filter network created with the speaker impedance and the coupling capacitance and is calculated with equation 8.
fc
+ 2 pR1 C
(8)
LC
For example, a 68-F capacitor with an 8- speaker would attenuate low frequencies below 293 Hz. The BTL configuration cancels the dc offsets, which eliminates the need for the blocking capacitors. Low-frequency performance is then limited only by the input network and speaker response. Cost and PCB space are also minimized by eliminating the bulky coupling capacitor.
VDD -3 dB
VO(PP)
CC RL
VO(PP)
fc
Figure 6. Single-Ended Configuration and Frequency Response Increasing power to the load does carry a penalty of increased internal power dissipation. The increased dissipation is understandable considering that the BTL configuration produces 4x the output power of the SE configuration. Internal dissipation versus output power is discussed further in the crest factor and thermal considerations section.
single-ended operation
In SE mode (see Figure 5 and Figure 6), the load is driven from the primary amplifier output for each channel (OUT+, terminals 2 and 14). The amplifier switches single-ended operation when the SE/BTL terminal is held high. This puts the negative outputs in a high-impedance state, and reduces the amplifier's gain to 1 V/V.
BTL amplifier efficiency
Class-AB amplifiers are notoriously inefficient. The primary cause of these inefficiencies is voltage drop across the output stage transistors. There are two components of the internal voltage drop. One is the headroom or dc voltage drop that varies inversely to output power. The second component is due to the sinewave nature of the output. The total voltage drop can be calculated by subtracting the RMS value of the output voltage from VDD. The internal voltage drop multiplied by the RMS value of the supply current, IDDrms, determines the internal power dissipation of the amplifier.
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POST OFFICE BOX 655303
* DALLAS, TEXAS 75265
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION
An easy-to-use equation to calculate efficiency starts out being equal to the ratio of power from the power supply to the power delivered to the load. To accurately calculate the RMS and average values of power in the load and in the amplifier, the current and voltage waveform shapes must first be understood (see Figure 7).
VO IDD
V(LRMS)
IDD(avg)
Figure 7. Voltage and Current Waveforms for BTL Amplifiers Although the voltages and currents for SE and BTL are sinusoidal in the load, currents from the supply are very different between SE and BTL configurations. In an SE application the current waveform is a half-wave rectified shape whereas in BTL it is a full-wave rectified waveform. This means RMS conversion factors are different. Keep in mind that for most of the waveform both the push and pull transistors are not on at the same time, which supports the fact that each amplifier in the BTL device only draws current from the supply for half the waveform. The following equations are the basis for calculating amplifier efficiency.
Efficiency of a BTL amplifier
+ PP L
SUP
(9)
VP 2
Where:
PL
+
V Lrms 2 RL
, and V LRMS
+
, therefore, P L 1 +p
+ 2R
VP VP RL
2 L
and P SUP Therefore,
P SUP
+ VDD IDDavg + 2 VDD VP pR
L
p
0
and
I DDavg
sin(t) dt
+1 p
VP RL
[cos(t)]
p
0
+ p2VP R
L
substituting PL and PSUP into equation 9,
Efficiency of a BTL amplifier
+2 V
VP 2 RL
DD V P
2
+4V
p VP
DD
Where:
VP
+
p RL
2 PL RL
Therefore,
h BTL
PL = Power delivered to load PSUP = Power drawn from power supply VLRMS = RMS voltage on BTL load RL = Load resistance VP = Peak voltage on BTL load IDDavg = Average current drawn from the power supply VDD = Power supply voltage BTL = Efficiency of a BTL amplifier
+p
2 PL RL 4 V DD
(10)
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15
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION
Table 3 employs equation 10 to calculate efficiencies for four different output power levels. Note that the efficiency of the amplifier is quite low for lower power levels and rises sharply as power to the load is increased, resulting in a nearly flat internal power dissipation over the normal operating range. Note that the internal dissipation at full output power is less than in the half power range. Calculating the efficiency for a specific system is the key to proper power supply design. For a stereo 1-W audio system with 8- loads and a 5-V supply, the maximum draw on the power supply is almost 3.25 W. Table 3. Efficiency vs Output Power in 5-V 8- BTL Systems
OUTPUT POWER (W) 0.25 0.50 1.00 1.25 EFFICIENCY (%) 31.4 44.4 62.8 70.2 PEAK VOLTAGE (V) 2.00 2.83 4.00 4.47 INTERNAL DISSIPATION (W) 0.55 0.62 0.59 0.53
High peak voltages cause the THD to increase.
A final point to remember about Class-AB amplifiers (either SE or BTL) is how to manipulate the terms in the efficiency equation to utmost advantage when possible. Note that in equation 10, VDD is in the denominator. This indicates that as VDD goes down, efficiency goes up.
crest factor and thermal considerations
Class-AB power amplifiers dissipate a significant amount of heat in the package under normal operating conditions. A typical music CD requires 12 dB to 15 dB of dynamic range, or headroom above the average power output, to pass the loudest portions of the signal without distortion. In other words, music typically has a crest factor between 12 dB and 15 dB. When determining the optimal ambient operating temperature, the internal dissipated power at the average output power level must be used. From the TPA6010A4 data sheet, one can see that when the TPA6010A4 is operating from a 5-V supply into a 3- speaker that 4-W peaks are available. Converting watts to dB: P dB P + 10 Log P W + 10 Log 4 W + 6 dB 1W
ref
(11)
Subtracting the headroom restriction to obtain the average listening level without distortion yields: 6 dB - 15 dB = -9 dB (15 dB crest factor) 6 dB - 12 dB = -6 dB (12 dB crest factor) 6 dB - 9 dB = -3 dB (9 dB crest factor) 6 dB - 6 dB = 0 dB (6 dB crest factor) 6 dB - 3 dB = 3 dB (3 dB crest factor)
16
POST OFFICE BOX 655303
* DALLAS, TEXAS 75265
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION crest factor and thermal considerations (continued)
Converting dB back into watts: PW
+ 10PdB 10 Pref + 63 mW (18 dB crest factor) + 125 mW (15 dB crest factor) + 250 mW (9 dB crest factor) + 500 mW (6 dB crest factor) + 1000 mW (3 dB crest factor) + 2000 mW (15 dB crest factor)
(12)
This is valuable information to consider when attempting to estimate the heat dissipation requirements for the amplifier system. Comparing the absolute worst case, which is 2 W of continuous power output with a 3 dB crest factor, against 12 dB and 15 dB applications drastically affects maximum ambient temperature ratings for the system. Using the power dissipation curves for a 5-V, 3- system, the internal dissipation in the TPA6010A4 and maximum ambient temperatures is shown in Table 4. Table 4. TPA6010A4 Power Rating, 5-V, 3-, Stereo
PEAK OUTPUT POWER (W) 4 4 4 4 4 4 AVERAGE OUTPUT POWER 2 W (3 dB) 1000 mW (6 dB) 500 mW (9 dB) 250 mW (12 dB) 125 mW (15 dB) 63 mW (18 dB) POWER DISSIPATION (W/Channel) 1.7 1.6 1.4 1.1 0.8 0.6 MAXIMUM AMBIENT TEMPERATURE - 3C 6C 24C 51C 78C 96C
Table 5. TPA6010A4 Power Rating, 5-V, 8-, Stereo
PEAK OUTPUT POWER 2.5 W 2.5 W 2.5 W 2.5 W AVERAGE OUTPUT POWER 1250 mW (3 dB crest factor) 1000 mW (4 dB crest factor) 500 mW (7 dB crest factor) 250 mW (10 dB crest factor) POWER DISSIPATION (W/Channel) 0.55 0.62 0.59 0.53 MAXIMUM AMBIENT TEMPERATURE 100C 94C 97C 102C
The maximum dissipated power, PD(max), is reached at a much lower output power level for an 8- load than for a 3- load. As a result, this simple formula for calculating PD(max) may be used for an 8- application: P D(max)
DD + p2R L
2V 2
(13)
However, in the case of a 3- load, the PD(max) occurs at a point well above the normal operating power level. The amplifier may therefore be operated at a higher ambient temperature than required by the PD(max) formula for a 3- load.
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17
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION crest factor and thermal considerations (continued)
The maximum ambient temperature depends on the heat sinking ability of the PCB system. The derating factor for the PWP package is shown in the dissipation rating table (see page 4). Converting this to JA:
JA
1 1 + Derating Factor + 0.022 + 45C W
(14)
To calculate maximum ambient temperatures, first consider that the numbers from the dissipation graphs are per channel so the dissipated power needs to be doubled for two channel operation. Given JA, the maximum allowable junction temperature, and the total internal dissipation, the maximum ambient temperature can be calculated with the following equation. The maximum recommended junction temperature for the TPA6010A4 is 150C. The internal dissipation figures are taken from the Power Dissipation vs Output Power graphs. T A Max
+ TJ Max * JA PD + 150 * 45 (0.6 2) + 96C (15 dB crest factor)
(15)
NOTE: Internal dissipation of 0.6 W is estimated for a 2-W system with 15 dB crest factor per channel.
Tables 4 and 5 show that for some applications no airflow is required to keep junction temperatures in the specified range. The TPA6010A4 is designed with thermal protection that turns the device off when the junction temperature surpasses 150C to prevent damage to the IC. Table 4 and 5 were calculated for maximum listening volume without distortion. When the output level is reduced the numbers in the table change significantly. Also, using 8- speakers dramatically increases the thermal performance by increasing amplifier efficiency.
SE/BTL operation
The ability of the TPA6010A4 to easily switch between BTL and SE modes is one of its most important cost saving features. This feature eliminates the requirement for an additional headphone amplifier in applications where internal stereo speakers are driven in BTL mode but external headphone or speakers must be accommodated. Internal to the TPA6010A4, two separate amplifiers drive OUT+ and OUT-. The SE/BTL input (terminal 17) controls the operation of the follower amplifier that drives LOUT- and ROUT- (terminals 28 and 16). When SE/BTL is held low, the amplifier is on and the TPA6010A4 is in the BTL mode. When SE/BTL is held high, the OUT- amplifiers are in a high output impedance state, which configures the TPA6010A4 as an SE driver from LOUT+ and ROUT+ (terminals 2 and 14). IDD is reduced by approximately one-half in SE mode. Control of the SE/BTL input can be from a logic-level CMOS source or, more typically, from a resistor divider network as shown in Figure 8.
18
POST OFFICE BOX 655303
* DALLAS, TEXAS 75265
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION SE/BTL operation (continued)
RDOCKOUT 18 10 RHPIN 9 RLINEIN 11 RIN R MUX - + - + - + ROUT+ 14
- +
ROUT- 16
COUTR 330 F VDD 1 k
SE/BTL
100 k 17 100 k
Figure 8. TPA6010A4 Resistor Divider Network Circuit Using a readily available 1/8-in. (3.5 mm) stereo headphone jack, the control switch is closed when no plug is inserted. When closed the 100-k/1-k divider pulls the SE/BTL input low. When a plug is inserted, the 1-k resistor is disconnected and the SE/BTL input is pulled high. When the input goes high, the OUT- amplifier is shut down causing the speaker to mute (virtually open-circuits the speaker). The OUT+ amplifier then drives through the output capacitor (CO) into the headphone jack.
PC BEEP operation
The PC BEEP input allows a system beep to be sent directly from a computer through the amplifier to the speakers with few external components. The input is activated automatically. When the PC BEEP input is active, both of the LINEIN and HPIN inputs are deselected and both the left and right channels are driven in BTL mode with the signal from PC BEEP. The gain from the PC BEEP input to the speakers is fixed at 0.3 V/V and is independent of the volume setting. When the PC BEEP input is deselected, the amplifier will return to the previous operating mode and volume setting. Furthermore, if the amplifier is in shutdown mode, activating PC BEEP will take the device out of shutdown and output the PC BEEP signal, then return the amplifier to shutdown mode. The amplifier will automatically switch to PC BEEP mode after detecting a valid signal at the PC BEEP input. The preferred input signal is a square wave or pulse train with an amplitude of 1 Vpp or greater. To be accurately detected, the signal must have a minimum of 1 Vpp amplitude, rise and fall times of less than 0.1 s and a minimum of 8 rising edges. When the signal is no longer detected, the amplifier will return to its previous operating mode and volume setting.
POST OFFICE BOX 655303
* DALLAS, TEXAS 75265
19
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION PC BEEP operation (continued)
If it is desired to ac-couple the PC BEEP input, the value of the coupling capacitor should be chosen to satisfy the following equation:
C PCB
w 2p f
PCB
1 (100 kW)
(16)
The PC BEEP input can also be dc-coupled to avoid using this coupling capacitor. The pin normally sits at midrail when no signal is present.
Input MUX operation
RDOCKOUT 18 10 RHPIN 9 RLINEIN 11 RIN R MUX - + - + - + ROUT+ 14
- +
ROUT-
16
COUTR 330 F VDD 1 k
100 k
Figure 9. TPA6010A4 Example Input MUX Circuit Another advantage of using the MUX feature is setting the gain of the headphone channel to -1. This provides the optimum distortion performance into the headphones where clear sound is more important. Refer to the SE/BTL operation section for a description of the headphone jack control circuit.
20
POST OFFICE BOX 655303
* DALLAS, TEXAS 75265
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
APPLICATION INFORMATION shutdown modes
The TPA6010A4 employs a shutdown mode of operation designed to reduce supply current, IDD, to the absolute minimum level during periods of nonuse for battery-power conservation. The SHUTDOWN input terminal should be held high during normal operation when the amplifier is in use. Pulling SHUTDOWN low causes the outputs to mute and the amplifier to enter a low-current state. SHUTDOWN should never be left unconnected because amplifier operation would be unpredictable. Table 6. Shutdown and Mute Mode Functions
INPUTS SE/BTL Low X SHUTDOWN High Low AMPLIFIER STATE INPUT Line X OUTPUT BTL Mute SE
High High HP Inputs should never be left unconnected. X = do not care
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* DALLAS, TEXAS 75265
21
TPA6010A4 STEREO 2-W AUDIO POWER AMPLIFIER WITH BASS BOOST AND DC VOLUME CONTROL
SLOS268 - JUNE 2000
MECHANICAL DATA
PWP (R-PDSO-G**)
20-PIN SHOWN
PowerPADTM PLASTIC SMALL-OUTLINE PACKAGE
0,65 20
0,30 0,19 11
0,10 M
Thermal Pad (See Note D) 4,50 4,30 6,60 6,20 0,15 NOM
Gage Plane 1 A 10 0- 8 0,25 0,75 0,50
Seating Plane 1,20 MAX 0,15 0,05 PINS ** DIM A MAX A MIN 0,10
14 5,10 4,90
16 5,10 4,90
20 6,60 6,40
24 7,90 7,70
28 9,80 9,60 4073225/F 10/98
NOTES: A. B. C. D.
All linear dimensions are in millimeters. This drawing is subject to change without notice. Body dimensions do not include mold flash or protrusions. The package thermal performance may be enhanced by bonding the thermal pad to an external thermal plane. This pad is electrically and thermally connected to the backside of the die and possibly selected leads. E. Falls within JEDEC MO-153
For the latest package information, go to http://www.ti.com/sc/docs/package/pkg_info.htm PowerPAD is a trademark of Texas Instruments.
22
POST OFFICE BOX 655303
* DALLAS, TEXAS 75265
IMPORTANT NOTICE Texas Instruments and its subsidiaries (TI) reserve the right to make changes to their products or to discontinue any product or service without notice, and advise customers to obtain the latest version of relevant information to verify, before placing orders, that information being relied on is current and complete. All products are sold subject to the terms and conditions of sale supplied at the time of order acknowledgment, including those pertaining to warranty, patent infringement, and limitation of liability. TI warrants performance of its semiconductor products to the specifications applicable at the time of sale in accordance with TI's standard warranty. Testing and other quality control techniques are utilized to the extent TI deems necessary to support this warranty. Specific testing of all parameters of each device is not necessarily performed, except those mandated by government requirements. Customers are responsible for their applications using TI components. In order to minimize risks associated with the customer's applications, adequate design and operating safeguards must be provided by the customer to minimize inherent or procedural hazards. TI assumes no liability for applications assistance or customer product design. TI does not warrant or represent that any license, either express or implied, is granted under any patent right, copyright, mask work right, or other intellectual property right of TI covering or relating to any combination, machine, or process in which such semiconductor products or services might be or are used. TI's publication of information regarding any third party's products or services does not constitute TI's approval, warranty or endorsement thereof.
Copyright (c) 2000, Texas Instruments Incorporated

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