View ADA4860-1YRJZ-R2_1112131.PDF datasheet online --- IC-ON-LINE

Datasheet File OCR Text:

High Speed, Low Cost, Op Amp ADA4860-1
FEATURES
High speed 800 MHz, -3 dB bandwidth 790 V/s slew rate 8 ns settling time to 0.5% Wide supply range: 5 V to 12 V Low power: 6 mA 0.1 dB flatness: 125 MHz Differential gain: 0.02% Differential phase: 0.02 Low voltage offset: 3.5 mV (typ) High output current: 25 mA Power down
PIN CONFIGURATION
VOUT 1 -VS 2 +IN 3
6
+VS POWER DOWN -IN
05709-001
+
-
5
4
Figure 1. 6-Lead SOT-23 (RJ-6)
APPLICATIONS
Consumer video Professional video Broadband video ADC buffers Active filters
GENERAL DESCRIPTION
The ADA4860-1 is a low cost, high speed, current feedback op amp that provides excellent overall performance. The 800 MHz, -3 dB bandwidth, and 790 V/s slew rate make this amplifier well suited for many high speed applications. With its combination of low price, excellent differential gain (0.02%), differential phase (0.02), and 0.1 dB flatness out to 125 MHz, this amplifier is ideal for both consumer and professional video applications. The ADA4860-1 is designed to operate on supply voltages as low as +5 V and up to 5 V using only 6 mA of supply current. To further reduce power consumption, the amplifier is equipped with a power-down feature that lowers the supply current to 0.25 mA. The ADA4860-1 is available in a 6-lead SOT-23 package and is designed to work over the extended temperature range of -40C to +105C.
6.3 G = +2 6.2 VOUT = 2V p-p RF = RG = 499 6.1
CLOSED-LOOP GAIN (dB)
6.0 5.9 5.8 5.7 5.6 5.5 5.4 5.3 0.1 1 10 FREQUENCY (MHz) 100
05709-003
VS = +5V VS = 5V
1000
Figure 2. 0.1 dB Flatness
Rev. 0
Information furnished by Analog Devices is believed to be accurate and reliable. However, no responsibility is assumed by Analog Devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. Specifications subject to change without notice. No license is granted by implication or otherwise under any patent or patent rights of Analog Devices. Trademarks and registered trademarks are the property of their respective owners.
One Technology Way, P.O. Box 9106, Norwood, MA 02062-9106, U.S.A. Tel: 781.329.4700 www.analog.com Fax: 781.461.3113 (c)2006 Analog Devices, Inc. All rights reserved.
ADA4860-1 TABLE OF CONTENTS
Features .............................................................................................. 1 Applications....................................................................................... 1 Pin Configuration............................................................................. 1 General Description ......................................................................... 1 Revision History ............................................................................... 2 Specifications..................................................................................... 3 Absolute Maximum Ratings............................................................ 5 Thermal Resistance ...................................................................... 5 ESD Caution.................................................................................. 5 Typical Performance Characteristics ............................................. 6 Application Information................................................................ 14 Power Supply Bypassing ............................................................ 14 Feedback Resistor Selection...................................................... 14 Driving Capacitive Loads.......................................................... 15 Power Down Pin......................................................................... 15 Video Amplifier.......................................................................... 15 Single-Supply Operation ........................................................... 15 Optimizing Flatness and Bandwidth ....................................... 16 Layout and Circuit Board Parasitics ........................................ 17 Outline Dimensions ....................................................................... 18 Ordering Guide .......................................................................... 18
REVISION HISTORY
4/06--Revision 0: Initial Version
Rev. 0 | Page 2 of 20
ADA4860-1 SPECIFICATIONS
VS = +5 V (@ TA = 25C, G = +2, RL = 150 referred to midsupply, CL = 4 pF, unless otherwise noted). For G = +2, RF = RG = 499 and for G = +1, RF = 550 . Table 1.
Parameter DYNAMIC PERFORMANCE -3 dB Bandwidth Conditions VO = 0.2 V p-p VO = 2 V p-p VO = 0.2 V p-p, RL = 75 G = +1, VO = 0.2 V p-p VO = 2 V p-p VO = 2 V p-p, RL = 75 VO = 2 V p-p VO = 2 V p-p VO = 2 V step fC = 1 MHz, VO = 2 V p-p fC = 5 MHz, VO = 2 V p-p f = 100 kHz f = 100 kHz, +IN/-IN RL = 150 RL = 150 -13 -2 -7 400 +IN -IN +IN VCM = 2 V to 3 V Enabled Power down Enabled Power down -52 Min Typ 460 165 430 650 58 45 695 560 8 -90/-102 -70/-76 4.0 1.5/7.7 0.02 0.03 -4.25 -1 +1.0 650 10 85 1.5 1.2 to 3.7 -56 0.5 1.8 -200 60 200 3.5 60/100 1.2 to 3.8 1 to 4 0.8 to 4.2 45 12 6.5 0.5 +13 +1 +10 Max Unit MHz MHz MHz MHz MHz MHz V/s V/s ns dBc dBc nV/Hz pA/Hz % Degrees mV A A k M pF V dB V V nA A ns s ns V V V mA V mA mA dB
Bandwidth for 0.1 dB Flatness +Slew Rate (Rising Edge) -Slew Rate (Falling Edge) Settling Time to 0.5% NOISE/DISTORTION PERFORMANCE Harmonic Distortion HD2/HD3 Input Voltage Noise Input Current Noise Differential Gain Differential Phase DC PERFORMANCE Input Offset Voltage +Input Bias Current -Input Bias Current Open-Loop Transresistance INPUT CHARACTERISTICS Input Resistance Input Capacitance Input Common-Mode Voltage Range Common-Mode Rejection Ratio POWER DOWN PIN Input Voltage Bias Current Turn-On Time Turn-Off Time OUTPUT CHARACTERISTICS Output Overdrive Recovery Time (Rise/Fall) Output Voltage Swing
Short-Circuit Current POWER SUPPLY Operating Range Total Quiescent Current Quiescent Current Power Supply Rejection Ratio +PSR
VIN = +2.25 V to -0.25 V RL = 75 RL = 150 RL = 1 k Sinking and sourcing
1.2 to 3.8 0.9 to 4.1
Enabled POWER DOWN pin = +VS +VS = 4 V to 6 V, -VS = 0 V
Rev. 0 | Page 3 of 20
5 4.5
5.2 0.2 -62
-60
ADA4860-1
VS = 5 V (@ TA = 25C, G = +2, RL = 150 , CL = 4 pF, unless otherwise noted). For G = +2, RF = RG = 499 and for G = +1, RF = 550 . Table 2.
Parameter DYNAMIC PERFORMANCE -3 dB Bandwidth Conditions VO = 0.2 V p-p VO = 2 V p-p VO = 0.2 V p-p, RL = 75 G = +1, VO = 0.2 V p-p VO = 2 V p-p VO = 2 V p-p, RL = 75 VO = 2 V p-p VO = 2 V p-p VO = 2 V step fC = 1 MHz, VO = 2 V p-p fC = 5 MHz, VO = 2 V p-p f = 100 kHz f = 100 kHz, +IN/-IN RL = 150 RL = 150 -13 -2 -7 400 +IN -IN +IN VCM = 2 V Enabled Power down Enabled Power down -55 Min Typ 520 230 480 800 125 70 980 790 8 -90/-102 -77/-94 4.0 1.5/7.7 0.02 0.02 -3.5 -1.0 +1.5 700 12 90 1.5 -3.8 to +3.7 -58 -4.4 -3.2 -250 130 200 3.5 45/90 2 3.1 4.1 85 12 8 0.5 +13 +1 +10 Max Unit MHz MHz MHz MHz MHz MHz V/s V/s ns dBc dBc nV/Hz pA/Hz % Degrees mV A A k M pF V dB V V nA A ns s ns V V V mA V mA mA dB dB
Bandwidth for 0.1 dB Flatness +Slew Rate (Rising Edge) -Slew Rate (Falling Edge) Settling Time to 0.5% NOISE/DISTORTION PERFORMANCE Harmonic Distortion HD2/HD3 Input Voltage Noise Input Current Noise Differential Gain Differential Phase DC PERFORMANCE Input Offset Voltage +Input Bias Current -Input Bias Current Open-Loop Transresistance INPUT CHARACTERISTICS Input Resistance Input Capacitance Input Common-Mode Voltage Range Common-Mode Rejection Ratio POWER DOWN PIN Input Voltage Bias Current Turn-On Time Turn-Off Time OUTPUT CHARACTERISTICS Output Overdrive Recovery Time (Rise/Fall) Output Voltage Swing
Short-Circuit Current POWER SUPPLY Operating Range Total Quiescent Current Quiescent Current Power Supply Rejection Ratio +PSR -PSR
VIN = 3.0 V RL = 75 RL = 150 RL = 1 k Sinking and sourcing
2.5 3.9
Enabled POWER DOWN pin = +VS +VS = +4 V to +6 V, -VS = -5 V +VS = +5 V, -VS = -4 V to -6 V, POWER DOWN pin = -VS
5 5
6 0.25 -64 -61
-62 -58
Rev. 0 | Page 4 of 20
ADA4860-1 ABSOLUTE MAXIMUM RATINGS
Table 3.
Parameter Supply Voltage Power Dissipation Common-Mode Input Voltage Differential Input Voltage Storage Temperature Range Operating Temperature Range Lead Temperature Junction Temperature Rating 12.6 V See Figure 3 -VS + 1 V to +VS - 1 V VS -65C to +125C -40C to +105C JEDEC J-STD-20 150C
The power dissipated in the package (PD) for a sine wave and a resistor load is the total power consumed from the supply minus the load power. PD = Total Power Consumed - Load Power
PD = VSUPPLY VOLTAGE x I SUPPLY CURRENT -
RMS output voltages should be considered.
(
)
VOUT 2 RL
Stresses above those listed under Absolute Maximum Ratings may cause permanent damage to the device. This is a stress rating only; functional operation of the device at these or any other conditions above those indicated in the operational section of this specification is not implied. Exposure to absolute maximum rating conditions for extended periods may affect device reliability.
Airflow across the ADA4860-1 helps remove heat from the package, effectively reducing JA. In addition, more metal directly in contact with the package leads and through holes under the device reduces JA. Figure 3 shows the maximum safe power dissipation in the package vs. the ambient temperature for the 6-lead SOT-23 (170C/W) on a JEDEC standard 4-layer board. JA values are approximations.
2.0
THERMAL RESISTANCE
MAXIMUM POWER DISSIPATION (W)
JA is specified for the worst-case conditions, that is, JA is specified for device soldered in circuit board for surface-mount packages. Table 4. Thermal Resistance
Package Type 6-lead SOT-23 JA 170 Unit C/W
1.5
1.0
Maximum Power Dissipation
The maximum safe power dissipation for the ADA4860-1 is limited by the associated rise in junction temperature (TJ) on the die. At approximately 150C, which is the glass transition temperature, the plastic changes its properties. Even temporarily exceeding this temperature limit can change the stresses that the package exerts on the die, permanently shifting the parametric performance of the amplifiers. Exceeding a junction temperature of 150C for an extended period can result in changes in silicon devices, potentially causing degradation or loss of functionality.
0.5
05709-002
0
-40 -30 -20 -10
0
10
20
30
40
50
60
70
80
90
100 110
AMBIENT TEMPERATURE (C)
Figure 3. Maximum Power Dissipation vs. Temperature for a 4-Layer Board
ESD CAUTION
ESD (electrostatic discharge) sensitive device. Electrostatic charges as high as 4000 V readily accumulate on the human body and test equipment and can discharge without detection. Although this product features proprietary ESD protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. Therefore, proper ESD precautions are recommended to avoid performance degradation or loss of functionality.
Rev. 0 | Page 5 of 20
ADA4860-1 TYPICAL PERFORMANCE CHARACTERISTICS
RL = 150 and CL = 4 pF, unless otherwise noted.
2 1 0 -1 -2 -3 -4 -5 -6 0.1 G = +5, RF = 348, RG = 86.6
05709-008
VS = 5V VOUT = 0.2V p-p
2 G = +1, RF = 550 1 0 -1 -2 -3 -4 -5
VS = 5V VOUT = 0.2V p-p
G = +1, RF = 550
NORMALIZED GAIN (dB)
G = +2, RF = RG = 499 G = -1, RF = RG = 499
NORMALIZED GAIN (dB)
G = +2, RF = RG = 499 G = -1, RF = RG = 499
G = +5, RF = 348, RG = 86.6 G = +10, RF = 348, RG = 38.3 1 10 FREQUENCY (MHz) 100
05709-007
G = +10, RF = 348, RG = 38.3 1 10 FREQUENCY (MHz) 100
1000
-6 0.1
1000
Figure 4. Small Signal Frequency Response for Various Gains
2 1 0 -1 -2 -3 G = +10, RF = 348, RG = 38.3 -4
05709-012
Figure 7. Small Signal Frequency Response for Various Gains
2 1 0 -1 -2 -3 -4 -5 -6 0.1 G = +1, RF = 550 G = +5, RF = 348, RG = 86.6 G = +2, RF = RG = 499 G = +10, RF = 348, RG = 38.3
VS = 5V VOUT = 2V p-p G = -1, RF = RG = 499
NORMALIZED GAIN (dB)
VS = 5V VOUT = 2V p-p
G = -1, RF = RG = 499
NORMALIZED GAIN (dB)
G = +5, RF = 348, RG = 86.6 G = +2, RF = RG = 499
-6 0.1
1
10 FREQUENCY (MHz)
100
1000
1
10 FREQUENCY (MHz)
100
1000
Figure 5. Large Signal Frequency Response for Various Gains
6.3 G = +2 6.2 VOUT = 2V p-p RF = RG = 499 6.1
CLOSED-LOOP GAIN (dB) CLOSED-LOOP GAIN (dB)
Figure 8. Large Signal Frequency Response for Various Gains
7 6 5 4 3 2 1
6.0 5.9 5.8 5.7 5.6 5.5 5.4 5.3 0.1 1 10 FREQUENCY (MHz) 100
05709-003
VOUT = 4V p-p VOUT = 2V p-p VOUT = 1V p-p
VS = +5V VS = 5V
1000
0 0.1
1
10 FREQUENCY (MHz)
100
1000
Figure 6. Large Signal 0.1 dB Flatness
Figure 9. Large Signal Frequency Response for Various Output Levels
Rev. 0 | Page 6 of 20
05709-014
VS = 5V G = +2 RF = RG = 499
05709-013
-5
G = +1, RF = 550
ADA4860-1
8 7
CLOSED-LOOP GAIN (dB)
VS = 5V G = +2 RG = RF VOUT = 0.2V p-p
7 RF = 301 6
CLOSED-LOOP GAIN (dB)
RF = 301 RF = 402 RF = 604
6 5 4 RF = 499 3 RF = 402 2
05709-009
5 RF = 499 4 3 2 1 VS = 5V G = +2 RG = RF VOUT = 2V p-p 1 10 FREQUENCY (MHz) 100
RF = 604
0 0.1
1
10 FREQUENCY (MHz)
100
1000
0 0.1
1000
Figure 10. Small Signal Frequency Response vs. RF
Figure 13. Large Signal Frequency Response vs. RF
2 1 0 -1
VS = 5V VOUT = 0.2V p-p RL = 75
2 G = +1, RF = 550 1 0 -1
VS = 5V VOUT = 0.2V p-p RL = 75
G = +1, RF = 550
NORMALIZED GAIN (dB)
NORMALIZED GAIN (dB)
G = +2, RF = RG = 499 -2 -3 -4
05709-006
G = +2, RF = RG = 499 -2 -3 -4
05709-005
-5 -6 0.1
-5 -6 0.1
1
10 FREQUENCY (MHz)
100
1000
1
10 FREQUENCY (MHz)
100
1000
Figure 11. Small Signal Frequency Response for Various Gains
Figure 14. Small Signal Frequency Response for Various Gains
2 1 0 -1
VS = 5V VOUT = 2V p-p RL = 75
NORMALIZED GAIN (dB)
2 1 0 -1
VS = 5V VOUT = 2V p-p RL = 75
NORMALIZED GAIN (dB)
G = +1, RF = 550 -2 -3 G = +2, RF = RG = 499 -4
05709-015
G = +1, RF = 550 -2 -3 G = +2, RF = RG = 499 -4
05709-016
-5 -6 0.1
-5 -6 0.1
1
10 FREQUENCY (MHz)
100
1000
1
10 FREQUENCY (MHz)
100
1000
Figure 12. Large Signal Frequency Response for Various Gains
Figure 15. Large Signal Frequency Response for Various Gains
Rev. 0 | Page 7 of 20
05709-004
1
ADA4860-1
-40 -50 -60
DISTORTION (dBc)
VS = 5V G = +1 RF = 550
-40 -50 -60
DISTORTION (dBc)
VS = 5V G = +2 RF = RG = 499
VOUT = 3V p-p, HD3
VOUT = 2V p-p, HD2
-70 VOUT = 3V p-p, HD2 -80 VOUT = 2V p-p, HD2 -90 VOUT = 2V p-p, HD3
05709-017
-70 VOUT = 3V p-p, HD2 -80 VOUT = 3V p-p, HD3 -90 VOUT = 2V p-p, HD3
-110
1
10 FREQUENCY (MHz)
100
-110
1
10 FREQUENCY (MHz)
100
Figure 16. Harmonic Distortion vs. Frequency
Figure 19. Harmonic Distortion vs. Frequency
-40 -50 -60
DISTORTION (dBc)
VS = 5V G = +1 RF = 550
-40 VOUT = 2V p-p, HD2 -50 VOUT = 2V p-p, HD3 -60
DISTORTION (dBc)
VS = 5V G = +2 RF = RG = 499 VOUT = 2V p-p, HD3 VOUT = 2V p-p, HD2
-70 -80 -90 VOUT = 1V p-p, HD2 VOUT = 1V p-p, HD3
-70 -80 -90 VOUT = 1V p-p, HD2 VOUT = 1V p-p, HD3
05709-018
-110
1
10 FREQUENCY (MHz)
100
-110
1
10 FREQUENCY (MHz)
100
Figure 17. Harmonic Distortion vs. Frequency
Figure 20. Harmonic Distortion vs. Frequency
-40 -50 -60
DISTORTION (dBc)
G = +1 RF = 550 RL = 100 VOUT = 2V p-p, HD2 VS = 5V VOUT = 1V p-p, HD2 VS = +5V
-40 -50 -60
DISTORTION (dBc)
G = +2 RF = RG = 499 RL = 100
VOUT = 1V p-p, HD2 VS = +5V
VOUT = 2V p-p, HD2 VS = 5V VOUT = 2V p-p, HD3 VS = 5V
-70 -80 -90
-70 -80 -90
VOUT = 2V p-p, HD3 VS = 5V VOUT = 1V p-p, HD3 VS = +5V
05709-061
VOUT = 1V p-p, HD3 VS = +5V
-110
1
10 FREQUENCY (MHz)
100
-110
1
10 FREQUENCY (MHz)
100
Figure 18. Harmonic Distortion vs. Frequency for Various Supplies
Figure 21. Harmonic Distortion vs. Frequency for Various Supplies
Rev. 0 | Page 8 of 20
05709-062
-100
-100
05709-019
-100
-100
05709-041
-100
-100
ADA4860-1
200 VS = +5V 2.7 200 VS = +5V 2.7
OUTPUT VOLTAGE (mV) VS = 5V
OUTPUT VOLTAGE (mV) VS = 5V
100 VS = 5V 0
2.6
100 VS = 5V 0
2.6
OUTPUT VOLTAGE (V) +VS = 5V, -VS = 0V
2.5
2.5
-100 G = +1 VOUT = 0.2V p-p RF = 550 TIME = 5ns/DIV -200
2.4
-100 G = +2 VOUT = 0.2V p-p RF = RG = 499 TIME = 5ns/DIV
2.4
05709-033
2.3
-200
2.3
Figure 22. Small Signal Transient Response for Various Supplies
Figure 25. Small Signal Transient Response for Various Supplies
200 CL = 9pF CL = 4pF
200 CL = 9pF CL = 6pF
OUTPUT VOLTAGE (mV)
OUTPUT VOLTAGE (mV)
100
100
CL = 4pF 0
0 CL = 6pF -100 VS = 5V G = +1 VOUT = 0.2V p-p RF = 550 TIME = 5ns/DIV
-100
05709-034
-200
-200
VS = 5V G = +2 VOUT = 0.2V p-p RF = RG = 499 TIME = 5ns/DIV
Figure 23. Small Signal Transient Response for Various Capacitor Loads
Figure 26. Small Signal Transient Response for Various Capacitor Loads
2.7 CL = 6pF CL = 4pF 2.6
2.7 CL = 9pF CL = 6pF 2.6 CL = 9pF
OUTPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
CL = 4pF 2.5
2.5
2.4
05709-035
2.3
VS = 5V G = +1 VOUT = 0.2V p-p RF = 550 TIME = 5ns/DIV
2.4
2.3
VS = 5V G = +2 VOUT = 0.2V p-p RF = RG = 499 TIME = 5ns/DIV
Figure 24. Small Signal Transient Response for Various Capacitor Loads
Figure 27. Small Signal Transient Response for Various Capacitor Loads
Rev. 0 | Page 9 of 20
05709-022
05709-021
05709-020
OUTPUT VOLTAGE (V) +VS = 5V, -VS = 0V
ADA4860-1
1.5 VS = 5V 1.0 VS = +5V 3.5 1.0 4.0 1.5 VS = 5V VS = +5V 3.5 4.0
OUTPUT VOLTAGE (V) VS = 5V
OUTPUT VOLTAGE (V) +VS = 5V, -VS = 0V
OUTPUT VOLTAGE (V) VS = 5V
0.5
3.0
0.5
3.0
0
2.5
0
2.5
-0.5 G = +1 VOUT = 2V p-p RF = 550 TIME = 5ns/DIV
2.0
-0.5 G = +2 VOUT = 2V p-p RF = RG = 499 TIME = 5ns/DIV
2.0
-1.0
1.5
05709-036
-1.0
1.5
05709-023
05709-025 05709-024
-1.5
1.0
-1.5
1.0
Figure 28. Large Signal Transient Response for Various Supplies
Figure 31. Large Signal Transient Response for Various Supplies
1.5
CL = 9pF
1.5 CL = 6pF 1.0
CL = 9pF
CL = 6pF
1.0
OUTPUT VOLTAGE (V)
0.5
OUTPUT VOLTAGE (V)
CL = 4pF
0.5
CL = 4pF
0
0
-0.5 VS = 5V G = +1 VOUT = 2V p-p RF = 550 TIME = 5ns/DIV
-0.5 VS = 5V G = +2 VOUT = 2V p-p RF = RG = 499 TIME = 5ns/DIV
-1.0
-1.0
05709-037
-1.5
-1.5
Figure 29. Large Signal Transient Response for Various Capacitor Loads
Figure 32. Large Signal Transient Response for Various Capacitor Loads
4.0
CL = 9pF
4.0 CL = 6pF 3.5
CL = 9pF
CL = 6pF
3.5
OUTPUT VOLTAGE (V)
OUTPUT VOLTAGE (V)
CL = 4pF 3.0
CL = 4pF 3.0
2.5
2.5
2.0 VS = 5V G = +1 VOUT = 2V p-p RF = 550 TIME = 5ns/DIV
2.0 VS = 5V G = +2 VOUT = 2V p-p RF = RG = 499 TIME = 5ns/DIV
1.5
1.5
05709-039
1.0
1.0
Figure 30. Large Signal Transient Response for Various Capacitor Loads
Figure 33. Large Signal Transient Response for Various Capacitor Loads
Rev. 0 | Page 10 of 20
OUTPUT VOLTAGE (V) +VS = 5V, -VS = 0V
ADA4860-1
2500 VS = 5V G = +1 RF = 550 1600 1400 1200 VS = 5V G = +2 RF = RG = 499
2000
SLEW RATE (V/s)
SLEW RATE (V/s)
POSITIVE SLEW RATE 1500
POSITIVE SLEW RATE 1000 800 NEGATIVE SLEW RATE 600 400
1000 NEGATIVE SLEW RATE 500
05709-043
0
0
0.5
1.0
1.5
2.0
2.5
3.0
3.5
4.0
4.5
0
0
0.25
0.50
0.75
1.00
1.25
1.50
1.75
2.00
2.25
INPUT VOLTAGE (V p-p)
INPUT VOLTAGE (V p-p)
Figure 34. Slew Rate vs. Input Voltage
Figure 37. Slew Rate vs. Input Voltage
900 800 700
SLEW RATE (V/s) SLEW RATE (V/s)
900 VS = 5V G = +1 RF = 550 800 700 POSITIVE SLEW RATE 600 500
VS = 5V G = +2 RF = RG = 499 POSITIVE SLEW RATE
600 500 NEGATIVE SLEW RATE 400 300
05709-026
NEGATIVE SLEW RATE 400 300
05709-029
200 100
200 100
0
0.5
1.0
1.5
2.0
2.5
0
0.25
0.50
0.75
1.00
1.25
INPUT VOLTAGE (V p-p)
INPUT VOLTAGE (V p-p)
Figure 35. Slew Rate vs. Input Voltage
Figure 38. Slew Rate vs. Input Voltage
1.00 VIN 0.75 0.50
SETTLING TIME (%)
1.00 0.75 0.50
SETTLING TIME (%)
t = 0s
VS = 5V G = +2 VOUT = 2V p-p RF = RG = 499 TIME = 5ns/DIV
0.25 1V 0 -0.25 -0.50 -0.75 -1.00 t = 0s VS = 5V G = +2 VOUT = 2V p-p RF = RG = 499 TIME = 5ns/DIV
0.25 1V 0 -0.25 -0.50
05709-027
-1.00
VIN
Figure 36. Settling Time Rising Edge
Figure 39. Settling Time Falling Edge
Rev. 0 | Page 11 of 20
05709-030
-0.75
05709-028
200
ADA4860-1
30 VS = 5V, +5V
INPUT VOLTAGE NOISE (nV/ Hz) INPUT CURRENT NOISE (pA/ Hz)
110 100 90 80 70 60 50 40 30 20 10 0 10 100 1k 10k 100k 1M 10M NONINVERTING INPUT INVERTING INPUT
05709-032
VS = 5V, +5V
25
20
15
10
5
05709-031
0 10
100
1k
10k
100k
1M
10M
100M
100M
FREQUENCY (Hz)
FREQUENCY (Hz)
Figure 40. Input Voltage Noise vs. Frequency
Figure 43. Input Current Noise vs. Frequency
0 -10 -20 -30 -40
VS = 5V G = +2 COMMON-MODE REJECTION (dB)
0 -10 -20 -30 -40 -50 -60
POWER SUPPLY REJECTION (dB)
VS = 5V VOUT = 200mV rms RF = 560
-PSR
+PSR -50 -60 -70 0.1
05709-053
1
10 FREQUENCY (MHz)
100
1000
-70 0.1
1
10 FREQUENCY (MHz)
100
1000
Figure 41. Power Supply Rejection vs. Frequency
Figure 44. Common-Mode Rejection vs. Frequency
6 5
OUTPUT AND INPUT VOLTAGE (V)
INPUT VOLTAGE x 2
3 2 1 0 -1 -2 -3 -4 -5 -6 0 100 200 300 400 500 600 700 800 900
05709-040
OUTPUT AND INPUT VOLTAGE (V)
4
VS = 5V G = +2 RF = RG = 499 f = 1MHz
5.5 5.0 4.5 4.0 3.5 3.0 2.5 2.0 1.5 1.0 0.5 0 -0.5 0 100 200 300 400 500 600 700 OUTPUT VOLTAGE INPUT VOLTAGE x 2
VS = 5V G = +2 RF = RG = 499 f = 1MHz
OUTPUT VOLTAGE
1000
800
900
1000
TIME (ns)
TIME (ns)
Figure 42. Output Overdrive Recovery
Figure 45. Output Overdrive Recovery
Rev. 0 | Page 12 of 20
05709-042
05709-055
ADA4860-1
1000 VS = 5V G = +2 0
40 30
TRANSIMPEDANCE (k)
100 TRANSIMPEDANCE PHASE 10
-45
PHASE (Degrees)
INPUT VOS (mV)
20 10 VS = 5V 0 -10 -20
05709-054
05709-058
VS = +5V
-90
1
-135
-30 -40 -5
0.1 0.01
0.1
1
10
100
-180 1000
-4
-3
-2
-1
0 VCM (V)
1
2
3
4
5
FREQUENCY (MHz)
Figure 46. Transimpedance and Phase vs. Frequency
Figure 49. Input VOS vs. Common-Mode Voltage
6.5 VS = 5V
TOTAL SUPPLY CURRENT (mA)
TOTAL SUPPLY CURRENT (mA)
7.0
6.0
6.5
6.0
5.5 VS = +5V 5.0
5.5
5.0
4.5
05709-059
4.5
05709-057
4.0 -40
4.0
-25
-10
5
20
35
50
65
80
95
110
125
4
5
6
7
8
9
10
11
12
TEMPERATURE (C)
SUPPLY VOLTAGE (V)
Figure 47. Supply Current at Various Supplies vs. Temperature
Figure 50. Supply Current vs. Supply Voltage
10 8 6
INPUT BIAS CURRENT (A)
VS = 5V VS = +5V
4 2 0 -2 -4 -6 -8 -10 -5 -4 -3 -2 -1 0 1
2
3
4
5
OUTPUT VOLTAGE (V)
Figure 48. Inverting Input Bias Current vs. Output Voltage
05709-056
Rev. 0 | Page 13 of 20
ADA4860-1 APPLICATION INFORMATION
POWER SUPPLY BYPASSING
Attention must be paid to bypassing the power supply pins of the ADA4860-1. High quality capacitors with low equivalent series resistance (ESR), such as multilayer ceramic capacitors (MLCCs), should be used to minimize supply voltage ripple and power dissipation. Generally, a 10 F tantalum capacitor located in close proximity to the ADA4860-1 is required to provide good decoupling for lower frequency signals. In addition, a 0.1 F decoupling multilayer ceramic chip capacitor (MLCC) should be located as close to each of the power supply pins as is physically possible, no more than inch away. The ground returns should terminate immediately into the ground plane. Locating the bypass capacitor return close to the load return minimizes ground loops and improves performance. Figure 51 and Figure 52 show the typical noninverting and inverting configurations and the recommended bypass capacitor values.
+VS 10F + 0.1F VIN +
ADA4860-1
- 0.1F 10F + RF RG -VS
VOUT
FEEDBACK RESISTOR SELECTION
The feedback resistor has a direct impact on the closed-loop bandwidth and stability of the current feedback op amp circuit. Reducing the resistance below the recommended value can make the amplifier response peak and even become unstable. Increasing the size of the feedback resistor reduces the closedloop bandwidth. Table 5 provides a convenient reference for quickly determining the feedback and gain set resistor values and bandwidth for common gain configurations. Table 5. Recommended Values and Frequency Performance1
-3 dB SS BW (MHz) 800 400 520 335 165 -3 dB LS BW (MHz) 165 400 230 265 195 Large Signal 0.1 dB Flatness 40 80 125 100 28
Figure 51. Noninverting Gain
RF +VS 10F + 0.1F VIN RG -
ADA4860-1
+ 0.1F 10F + -VS
VOUT
05709-010
Gain +1 -1 +2 +5 +10
1
RF () 550 499 499 348 348
RG () N/A 499 499 86.6 38.3
Figure 52. Inverting Gain
Conditions: VS = 5 V, TA = 25C, RL = 150 .
Rev. 0 | Page 14 of 20
05709-011
ADA4860-1
DRIVING CAPACITIVE LOADS
If driving loads with a capacitive component is desired, the best frequency response is obtained by the addition of a small series resistance, as shown in Figure 53. Figure 54 shows the optimum value for RSERIES vs. capacitive load. The test was performed with a 50 MHz, 50% duty cycle pulse, with an amplitude of 200 mV p-p. The criteria for RSERIES selection was based on maintaining approximately 1 dB of peaking in small signal frequency response. It is worth noting that the frequency response of the circuit can be dominated by the passive roll-off of RSERIES and CL.
ADA4860-1
VIN RSERIES CL RL
POWER DOWN PIN
The ADA4860-1 is equipped with a power-down function. The POWER DOWN pin allows the user to reduce the quiescent supply current when the amplifier is not being used. The power-down threshold levels are derived from the voltage applied to the -VS pin. When used in single-supply applications, this is especially useful with conventional logic levels. The amplifier is powered down when the voltage applied to the POWER DOWN pin is greater than (-VS + 0.5 V). The amplifier is enabled whenever the POWER DOWN pin is left open, or the voltage on the POWER DOWN pin is less than (-VS + 0.5 V). If the POWER DOWN pin is not used, it should be connected to the negative supply.
RF 750
05709-052
VIDEO AMPLIFIER
With low differential gain and phase errors and wide 0.1 dB flatness, the ADA4860-1 is an ideal solution for consumer and professional video applications. Figure 55 shows a typical video driver set for a noninverting gain of +2, where RF = RG = 499 . The video amplifier input is terminated into a shunt 75 resistor. At the output, the amplifier has a series 75 resistor for impedance matching to the video load.
RF
Figure 53. Driving Capacitive Loads
14 12
SERIES RESISTANCE ()
10 8 6 4 2 0
+VS
10F + 0.1F
RG
05709-060
-
ADA4860-1
+
75 CABLE VIN 75 -VS
75 0.1F
75 CABLE VOUT 75
0
10
20
30
40
50
CAPACITIVE LOAD (pF)
Figure 54. Recommended RSERIES vs. Capacitive Load
10F +
05709-038
Figure 55. Video Driver Schematic
SINGLE-SUPPLY OPERATION
Single-supply operation can present certain challenges for the designer. For a detailed explanation on op amp single-supply operation, see Application Note AN-581.
Rev. 0 | Page 15 of 20
ADA4860-1
OPTIMIZING FLATNESS AND BANDWIDTH
When using the ADA4860-1, a variety of circuit conditions and parasitics can affect peaking, gain flatness, and -3 dB bandwidth. This section discusses how the ADA4860-1 small signal responses can be dramatically altered with basic circuit changes and added stray capacitances, see the Layout and Circuit Board Parasitics section for more information. Particularly with low closed-loop gains, the feedback resistor (Rf) effects peaking and gain flatness. However, with gain = +1, -3 dB bandwidth varies slightly, while gain = +2 has a much larger variation. For gain = +1, Figure 56 shows the effect that various feedback resistors have on frequency response. In Figure 56, peaking is wide ranging yet -3 dB bandwidths vary by only 6%. In this case, the user must pick what is desired: more peaking or flatter bandwidth. Figure 57 shows gain = +2 bandwidth and peaking variations vs. RF and RL. Bandwidth delta vs. RL increase was approximately 17%. As RF is reduced from 560 to 301 , the -3 dB bandwidth changes 49%, with excessive compromises in peaking, see Figure 57. For more gain = +2 bandwidth variations vs. RF, see Figure 10 and Figure 13.
2 VS = 5V G = +1 1 VOUT = 0.1V p-p RL = 100
NORMALIZED GAIN (dB)
The impact of resistor case sizes was observed using the circuit drawn in Figure 58. The types and sizes chosen were 0402 case sized thin film and 1206 thick film. All other measurement conditions were kept constant except for the case size and resistor composition.
DASH LINE IS PLANE CLEAR OUT AREA (EXCEPT SUPPLY PINS) DURING PC LAYOUT.
+ 49.9 - RF ADDED C J EXAMPLE
49.9 50 ADDED C LOAD EXAMPLE
Figure 58. Noninverting Gain Setup for Illustration of Parasitic Effects, 50 System, RL = 100
In Figure 59, a slight -3 dB bandwidth delta of approximately +10% can be seen going from a small-to-large case size. The increase in bandwidth with the larger 1206 case size is caused by an increase in parasitic capacitance across the chip resistor.
1
RF = 560 0 RF = 680
NORMALIZED GAIN (dB)
0 -1 -2 -3 -4 RF = 1.5k
-1 -2 -3 -4 VS = 5V G = +2 VOUT = 0.1V p-p -5 RG = RF = 560 RL = 100 -6 1 10 1206 RESISTOR SIZE
RF = 910
05709-049
RG
-6
05709-044
-5
0402 RESISTOR SIZE 100
1
10
100 FREQUENCY (MHz)
1000
10000
1000
FREQUENCY (MHz)
Figure 56. Small Signal Frequency Response vs. RF
2 VS = 5V G = +2 1 VOUT = 0.1V p-p RG = RF
NORMALIZED GAIN (dB)
Figure 59. Small Signal Frequency Response vs. Resistor Size
RF = 301, RL = 100
0 -1 -2 -3 -4
05709-045
RF = 560, RL = 100 RF = 560, RL = 1k
-5 -6
1
10
100
1000
FREQUENCY (MHz)
Figure 57. Small Signal Frequency Response vs. RF vs. RL
Rev. 0 | Page 16 of 20
05709-046
ADA4860-1
LAYOUT AND CIRCUIT BOARD PARASITICS
Careful attention to printed circuit board (PCB) layout prevents associated board parasitics from becoming problematic and affecting gain flatness and -3 dB bandwidth. In the printed circuit environment, parasitics around the summing junction (inverting input) or output pins can alter pulse and frequency response. Parasitic capacitance can be unintentionally created on a PC board via two parallel metal planes with a small vertical separation (in FR4). To avoid parasitic problems near the summing junction, signal line connections between the feedback and gain resistors should be kept as short as possible to minimize the inductance and stray capacitance. For similar reasons, termination and load resistors should be located as close as possible to the respective inputs. Removing the ground plane on all layers from the area near and under the input and output pins reduces stray capacitance. To illustrate the affects of parasitic capacitance, a small capacitor of 0.4 pF from the amplifiers summing junction (inverting input) to ground was intentionally added. This was done on two boards with equal and opposite gains of +2 and -2. Figure 60 reveals the effects of parasitic capacitance at the summing junction for both noninverting and inverting gain circuits. With gain = +2, the additional 0.4 pF of added capacitance created an extra 43% -3 dB bandwidth extension, plus some extra peaking. For gain = -2, a 5% increase in -3 dB bandwidth was created with an extra 0.4 pF on summing junction.
1 0
NORMALIZED GAIN (dB)
In a second test, 5.6 pF of capacitance was added directly at the output of the gain = +2 amplifier. Figure 61 shows the results. Extra output capacitive loading on the ADA4860-1 also causes bandwidth extensions, as seen in Figure 61. The effect on the gain = +2 circuit is more pronounced with lighter resistive loading (1 k). For pulse response behavior with added output capacitances, see Figure 23, Figure 24, Figure 26, Figure 27, Figure 29, Figure 30, Figure 32, and Figure 33.
3 VS = 5V G = +2 2V OUT = 0.1V p-p RF = RG = 560 1
NORMALIZED GAIN (dB)
RL = 1k, CL = 5.6pF EXTRA RL = 100, CL = 5.6pF EXTRA
0 -1 -2 -3 -4 -5 -6 RL = 1k, CL = 0pF RL = 100, CL = 0pF
1
10
100
1000
FREQUENCY (MHz)
Figure 61. Small Signal Frequency Response vs. Output Capacitive Load
G = +2, RF = 560, CJ = 0.4pF EXTRA
For more information on high speed board layout, go to: www.analog.com and www.analog.com/library/analogDialogue/archives/3909/layout.html.
-1 -2
G = -2, RF = 402, CJ = 0.4pF EXTRA G = -2, RF = 402, CJ = 0pF G = +2, RF = 560, CJ = 0pF
-3 -4 -5 VS = 5V VOUT = 0.1V p-p RL = 100 -6 1
10
100
1000
FREQUENCY (MHz)
Figure 60. Small Signal Frequency Response vs. Added Summing Junction Capacitance
05709-047
Rev. 0 | Page 17 of 20
05709-048
ADA4860-1 OUTLINE DIMENSIONS
2.90 BSC
6
5
4
1.60 BSC
1 2 3
2.80 BSC
PIN 1 INDICATOR 0.95 BSC 1.30 1.15 0.90 1.90 BSC
1.45 MAX 0.50 0.30
0.22 0.08 10 4 0 0.60 0.45 0.30
0.15 MAX
SEATING PLANE
COMPLIANT TO JEDEC STANDARDS MO-178-AB
Figure 62. 6-Lead Plastic Surface-Mount Package [SOT-23] (RJ-6) Dimensions shown in millimeters
ORDERING GUIDE
Model ADA4860-1YRJZ-RL 1 ADA4860-1YRJZ-RL71 ADA4860-1YRJZ-R21
1
Temperature Range -40C to +105C -40C to +105C -40C to +105C
Package Description 6-Lead SOT-23 6-Lead SOT-23 6-Lead SOT-23
Ordering Quantity 10,000 3,000 250
Package Option RJ-6 RJ-6 RJ-6
Branding HKB HKB HKB
Z = Pb-free part.
Rev. 0 | Page 18 of 20
ADA4860-1 NOTES
Rev. 0 | Page 19 of 20
ADA4860-1 NOTES
(c)2006 Analog Devices, Inc. All rights reserved. Trademarks and registered trademarks are the property of their respective owners. D05709-0-4/06(0)
Rev. 0 | Page 20 of 20

▲Up To Search▲

Price & Availability of ADA4860-1YRJZ-R2

	To Download ADA4860-1YRJZ-R2 Datasheet File
If you can't view the Datasheet, Please click here to try to view without PDF Reader .