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rev. 0 a information furnished by analog devices is believed to be accurate and reliable. however, no responsibility is assumed by analog devices for its use, nor for any infringements of patents or other rights of third parties that may result from its use. no license is granted by implication or otherwise under any patent or patent rights of analog devices. one technology way, p.o. box 9106, norwood, ma 02062-9106, u.s.a. tel: 781/329-4700www.analog.com fax: 781/326-8703 ? analog devices, inc., 2002 AD7484 3 msps, 14-bit sar adc features fast throughput rate: 3 msps wide input bandwidth: 40 mhz no pipeline delays with sar adc excellent dc accuracy performance two parallel interface modes low power: 90 mw (full power) and 2.5 mw (nap mode) standby mode: 2 a max single 5 v supply operation internal 2.5 v reference full-scale overrange mode (using 15th bit) system offset removal via user access offset register nominal 0 v to 2.5 v input with shifted range capability pin compatible upgrade of 12-bit ad7482 functional block diagram 2.5 v reference nap mode2 buf t/h av dd a gnd c bias dv dd dgnd refsel refout refin vin 14-bit algorithmic sar cs rd mode1 clip d0 stby d1 reset d2 d3 convst d4 d14 d5 d13 d6 d12 d11 d10 d9 d8 control logic and i/o registers d7 AD7484 v drive write busy general description the AD7484 is a 14-bit, high speed, low power, successive- approximation adc. the part features a parallel interface with throughput rates up to 3 msps. the part contains a low noise, wide bandwidth track-and-hold that can handle input fre- quencies in excess of 40 mhz. the conversion process is a proprietary algorithmic successive- approximation technique that results in no pipeline delays. the input signal is sampled and a conversion is initiated on the falling edge of the convst signal. the conversion process is controlled via an internally trimmed oscillator. interfacing is via standard parallel signal lines, making the part directly compatible with microcontrollers and dsps. the AD7484 provides excellent ac and dc performance specifi- cations. factory trimming ensures high dc accuracy resulting in very low inl, offset, and gain errors. the part uses advanced design techniques to achieve very low power dissipation at high throughput rates. power consumption in the normal mode of operation is 90 mw. there are two power- saving modes: a nap mode that keeps the reference circuitry alive for a quick power-up while consuming 2.5 mw, and a standby mode that reduces power consumption to a mere 10 w. the AD7484 features an on-board 2.5 v reference but can also accommodate an externally provided 2.5 v reference source. the nominal analog input range is 0 v to 2.5 v, but an offset shift capability allows this nominal range to be offset by 200 mv. this allows the user considerable flexibility in setting the bottom end reference point of the signal range, a useful feature when using single-supply op amps. the AD7484 also provides the user with an 8% overrange capa- bility via a 15th bit. thus, if the analog input range strays ou tside the nominal by up to 8%, the user can still accurately resolve the signal by using the 15th bit. the AD7484 is powered by a 4.75 v to 5.25 v supply. the part also provides a v drive pin that allows the user to set the voltage levels for the digital interface lines. the range for this v drive p in is from 2.7 v to 5.25 v. the part is housed in a 48-lead lqfp package and is specified over a C 40 c to +85 c temperature range.
rev. 0 C2C AD7484?pecifications 1 parameter specification unit test conditions/comments dynamic performance 2,3 signal-to-noise + distortion (sinad) 4 76.5 db min f in = 1 mhz 78 db typ f in = 1 mhz 79 db typ f in = 1 mhz, extended input 77 db typ f in = 1 mhz, internal reference total harmonic distortion (thd) 4 C 90 db max C 95 db typ C 92 db typ internal reference peak harmonic or spurious noise (sfdr) 4 C 90 db max intermodulation distortion (imd) 4 second order terms C 96 db typ f in1 = 95.053 khz, f in2 = 105.329 khz third order terms C 94 db typ aperture delay 10 ns typ full-power bandwidth 40 mhz typ @ 3 db 3.5 mhz typ @ 0.1 db dc accuracy resolution 14 bits integral nonlinearity 4 1 lsb max 0.5 lsb typ differential nonlinearity 4 0.75 lsb max guaranteed no missed codes to 14 bits 0.3 lsb typ offset error 4 6 lsb max 0.036 %fsr max gain error 4 6 lsb max 0.036 %fsr max analog input input voltage C 200 mv min +2.7 v max dc leakage current 1 a max v in from 0 v to 2.7 v 2 a typ v in = C 200 mv input capacitance 5 35 pf typ reference input/output v refin input voltage +2.5 v 1% for specified performance v refin input dc leakage current 1 a max v refin input capacitance 5 25 pf typ v refin input current 220 a typ external reference v refout output voltage +2.5 v typ v refout error @ 25 c 50 mv typ v refout error t min to t max 100 mv max v refout output impedance 1 ? typ logic inputs input high voltage, v inh v drive C 1v min input low voltage, v inl 0.4 v max input current, i in 1 a max input capacitance, c in 5 10 pf max logic outputs output high voltage, v oh 0.7 v drive v min output low voltage, v ol 0.3 v drive v max floating-state leakage current 10 a max floating-state output capacitance 5 10 pf max output coding straight (natural) binary conversion rate conversion time 300 ns max track-and-hold acquisition time (t acq )7 0 ns max sine wave input 70 ns max full-scale step input throughput rate 2.5 msps max parallel mode 1 3m sps max parallel mode 2 (v dd = 5 v 5%, agnd = dgnd = 0 v, v ref = external, f sample = 3 msps; all specifica- tions t min to t max and valid for v drive = 2.7 v to 5.25 v, unless otherwise noted.)
rev. 0 AD7484 C3C parameter specification unit test conditions/comments power requirements v dd 5v 5% v drive 2.7 v min 5.25 v max i dd normal mode (static) 12 ma max cs and rd = logic 1 normal mode (operational) 18 ma max nap mode 0.5 ma max standby mode 2 a max 0.5 a typ power dissipation normal mode (operational) 90 mw max nap mode 2.5 mw max standby mode 6 10 w max notes 1 temperature ranges as follows: C 40 c to +85 c. 2 snr and sinad figures quoted include external analog input circuit noise contribution of approximately 1 db. 3 see typical performance characteristics section for analog input circuits used. 4 see terminology section. 5 sample tested @ 25 c to ensure compliance. 6 digital input levels at gnd or v drive . specifications subject to change without notice. (v dd = 5 v 5%, agnd = dgnd = 0 v, v ref = external, f sample = 3 msps; all specifications t min to t max and valid for v drive = 2.7 v to 5.25 v, unless otherwise noted.) specifications (continued) parameter symbol min typ max unit data read conversion time t conv 300 ns quiet time before conversion start t quiet 100 ns convst pulsewidth t 1 5ns convst falling edge to busy falling edge t 2 20 ns cs falling edge to rd falling edge t 3 0ns data access time t 4 25 ns convst falling edge to new data valid t 5 30 ns busy rising edge to new data valid t 6 5ns bus relinquish time t 7 10 ns rd rising edge to cs rising edge t 8 0ns cs pulsewidth t 14 30 ns rd pulsewidth t 15 30 ns data write write pulsewidth t 9 5ns data setup time t 10 2ns data hold time t 11 6ns cs falling edge to write falling edge t 12 5ns write falling edge to cs rising edge t 13 0ns * all timing specifications given above are with a 25 pf load capacitance. with a load capacitance greater than this value, a dig ital buffer or latch must be used. specifications subject to change without notice. timing characteristics * (v dd = 5 v 5%, agnd = dgnd = 0 v, v ref = external; all specifications t min to t max and valid for v drive = 2.7 v to 5.25 v, unless otherwise noted.)
rev. 0 C4C AD7484 absolute maximum ratings * (t a = 25 c, unless otherwise noted.) v dd to gnd . . . . . . . . . . . . . . . . . . . . . . . . . . C 0.3 v to +7 v v drive to gnd . . . . . . . . . . . . . . . . . . . . . . . . C 0.3 v to +7 v analog input voltage to gnd . . . . . C 0.3 v to av dd + 0.3 v digital input voltage to gnd . . . . . C 0.3 v to v drive + 0.3 v refin to gnd . . . . . . . . . . . . . . . . C 0.3 v to av dd + 0.3 v input current to any pin except supplies . . . . . . . . . 10 ma operating temperature range commercial . . . . . . . . . . . . . . . . . . . . . . . . C 40 c to +85 c storage temperature range . . . . . . . . . . . . C 65 c to +150 c junction temperature . . . . . . . . . . . . . . . . . . . . . . . . . 150 c pin configuration 36 35 34 33 32 31 30 29 28 27 26 25 13 14 15 16 17 18 19 20 21 22 23 24 1 2 3 4 5 6 7 8 9 10 11 12 48 47 46 45 44 39 38 37 43 42 41 40 pin 1 identifier top view (not to scale) d10 d9 d8 d7 v drive dgnd dgnd av dd c bias a gnd a gnd av dd a gnd vin refout refin refsel a gnd dv dd d6 d5 d4 AD7484 a gnd d3 a gnd a gnd av dd clip mode1 mode2 reset convst d14 d13 d12 d11 av dd a gnd a gnd stby nap cs rd write busy d0 d1 d2 ja thermal impedance . . . . . . . . . . . . . . . . . . . . . . 50 c/w jc thermal impedance . . . . . . . . . . . . . . . . . . . . . . 10 c/w lead temperature, soldering vapor phase (60 secs) . . . . . . . . . . . . . . . . . . . . . . . 215 c infrared (15 secs) . . . . . . . . . . . . . . . . . . . . . . . . . . . 220 c esd . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . . 1 kv * stresses above those listed under absolute maximum ratings may cause perma- nent damage to the device. this is a stress rating only; functional operation of the device at these or any other conditions above those listed in the operational sections of this specification is not implied. exposure to absolute maximum rating condi- tions for extended periods may affect device reliability. caution esd (electrostatic discharge) sensitive device. electrostatic charges as high as 4000 v readily accumulate on the human body and test equipment and can discharge without detection. although the AD7484 features proprietary esd protection circuitry, permanent damage may occur on devices subjected to high energy electrostatic discharges. therefore, proper esd precautions are recommended to avoid performance degradation or loss of functionality. warning! esd sensitive device ordering guide model temperature range package description option AD7484bst C 40 c to +85 cl ow-profile quad flat pack st-48 eval-AD7484cb 1 evaluation board eval-control brd2 2 controller board notes 1 this can be used as a standalone evaluation board or in conjunction with the eval-control board for evaluation/demonstration pu rposes. 2 this board is a complete unit allowing a pc to control and communicate with all analog devices evaluation boards ending in the cb designators.
rev. 0 AD7484 C5C pin function descriptions pin number mnemonic description 1, 5, 13, 46 av dd positive power supply for analog circuitry 2c bias decoupling pin for internal bias voltage. a 1 nf capacitor should be placed between this pin and agnd. 3, 4, 6, 11, 12, agnd power supply ground for analog circuitry 14, 15, 47, 48 7v in analog input. single-ended analog input channel. 8 refout reference output. refout connects to the output of the internal 2.5 v reference buffer. a 470 nf capacitor must be placed between this pin and agnd. 9 refin reference input. a 470 nf capacitor must be placed between this pin and agnd. when using an external voltage reference source, the reference voltage should be applied to this pin. 10 refsel reference decoupling pin. when using the internal reference, a 1 nf capacitor must be connected from this pin to agnd. when using an external reference source, this pin should be connected directly to agnd. 16 stby standby logic input. when this pin is logic high, the device will be placed in standby mode. see power saving section for further details. 17 nap nap logic input. when this pin is logic high, the device will be placed in a very low power mode. see power saving section for further details. 18 cs chip select logic input. this pin is used in conjunction with rd to access the conversion result. the databus is brought out of three-state and the current contents of the output register driven onto the data lines following the falling edge of both cs and rd . cs is also used in conjunction with write to perform a write to the offset register. cs can be hardwired permanently low. 19 rd read logic input. used in conjunction with cs to access the conversion result. 20 write write logic input. used in conjunction with cs to write data to the offset register. when the desired offset word has been placed on the databus, the write line should be pulsed high. it is the falling edge of this pulse that latches the word into the offset register. 21 busy busy logic output. this pin indicates the status of the conversion process. the busy signal goes low after the falling edge of convst and stays low for the duration of the conversion. in parallel mode 1, the busy signal returns high when the conversion result has been latched into the output register. in parallel mode 2, the busy signal returns high as soon as the conversion has been com- pleted, but the conversion result does not get latched into the output register until the falling edge of the next convst pulse. 22 C 28, 33 C 39 d0 C d1 3 data i/o bits (d13 is msb). these are three-state pins that are controlled by cs , rd , and write. the operating voltage level for these pins is determined by the v drive input. 29 dv dd positive power supply for digital circuitry 30, 31 dgnd ground reference for digital circuitry 32 v drive logic power supply input. the voltage supplied at this pin will determine at what voltage the interface logic of the device will operate. 40 d14 data output bit for overranging. if the overrange feature is not used, this pin should be pulled to dgnd via a 100 k ? resistor. 41 convst convert start logic input. a conversion is initiated on the falling edge of the convst signal. t he input track-and-hold amplifier goes from track mode to hold mode and the conversion process com mences. 42 reset reset logic input. a falling edge on this pin resets the internal state machine and terminates a conversion that may be in progress. the contents of the offset register will also be cleared on this edge. holding this pin low keeps the part in a reset state. 43 mode2 operating mode logic input. see table iii for details. 44 mode1 operating mode logic input. see table iii for details. 45 clip logic input. a logic high on this pin enables output clipping. in this mode, any input voltage that is greater than positive full scale or less than negative full scale will be clipped to all 1s or all 0s, respectively. further details are given in the offset/overrange section.
rev. 0 C6C AD7484 terminology integral nonlinearity this is the maximum deviation from a straight line passing through the endpoints of the adc transfer function. the end- points of the transfer function are zero scale, a point 1/2 lsb below the first code transition, and full scale, a point 1/2 lsb above the last code transition. differential nonlinearity this is the difference between the measured and ideal 1 lsb change between any two adjacent codes in the adc. offset error this is the deviation of the first code transition (00 . . . 000) to (00 . . . 001) from the ideal, i.e., agnd + 0.5 lsb. gain error this is the deviation of the last code transition (111 . . . 110) to (111 . . . 111) from the ideal (i.e., v ref C 1.5 lsb) after the offset error has been adjusted out. track-and-hold acquisition time track-and-hold acquisition time is the time required for the output of the track-and-hold amplifier to reach its final value, within 1/2 lsb, after the end of conversion (the point at which the track-and-hold returns to track mode). signal-to-(noise + distortion) ratio this is the measured ratio of signal-to-(noise + distortion) at the output of the a/d converter. the signal is the rms ampli tude of the fundamental. noise is the sum of all nonfundamental signals up to half the sampling frequency (f s /2), excluding dc. the ratio is dependent on the number of quantization levels in the digitization process; the more levels, the smaller the quanti- zation noise. the theoretical signal-to- ( noise + distortion ) ratio for an ideal n -bit converter with a sine wave input is given by: signal to noise distortion n db ?? + = + () ().. 602 176 thus, for a 14-bit converter this is 86.04 db . total harmonic distortion total harmonic distortion ( thd ) is the ratio of the rms sum of the harmonics to the fundamental. for the AD7484, it is defined as: thd db log vvvvv v () = ++++ 20 2 2 3 2 4 2 5 2 6 2 1 where v 1 is the rms amplitude of the fundamental and v 2 , v 3 , v 4 , v 5 , and v 6 are the rms amplitudes of the second through the sixth harmonics. peak harmonic or spurious noise peak harmonic or spurious noise is defined as the ratio of the rms value of the next largest component in the adc output spectrum (up to f s /2 and excluding dc) to the rms value of the fundamental. normally, the value of this specification is deter- mined by the largest harmonic in the spectrum, but for adcs where the harmonics are buried in the noise floor, it will be a noise peak. intermodulation distortion with inputs consisting of sine waves at two frequencies, fa and fb, any active device with nonlinearities will create distortion products at sum and difference frequencies of mfa nfb, where m and n = 0, 1, 2, 3, and so on. intermodulation distortion terms are those for which neither m nor n are equal to zero. for exam ple, the second order terms include (fa + fb) and (fa C fb), while the third order terms include (2fa + fb), (2fa C fb), (fa + 2fb), and (fa C 2fb). the AD7484 is tested using the ccif standard where two input frequencies near the top end of the input bandwidth are used. in this case, the second order terms are usually distanced in frequency from the original sine waves, while the third order terms are usually at a frequency close to the input frequencies. as a result, the second and third order terms are specified sepa- rately. the calculation of the intermodulation distortion is as per the thd specification, where it is the ratio of the rms sum of the individual distortion products to the rms amplitude of the sum of the fundamentals expressed in dbs.
rev. 0 t ypical performance characteristics?d7484 C7C frequency ?khz 0 0 200 400 600 800 1400 db ?0 ?0 ?0 ?00 ?40 ?0 1000 1200 f in = 10.7khz snr = +78.9db snr + d = +78.8db thd = ?3.9db ?20 tpc 1. 64k fft plot with 10 khz input tone frequency ?khz 0 0 200 400 600 800 1400 db ?0 ?0 ?0 ?00 ?40 ?0 1000 1200 f in = 1.013mhz snr = +77.7db snr + d = +77.6db thd = ?5.5db ?20 tpc 2. 64k fft plot with 1 mhz input tone adc ?code 1.0 0 4096 8192 16384 dnl ?lsb 0.8 0.2 ?.6 ?.8 ?.0 ?.4 12288 0.6 0 0.4 ?.2 tpc 3. typical dnl adc ?code 1.0 0 4096 8192 16384 inl ?lsb 0.8 0.2 ?.6 ?.8 ?.0 ?.4 12288 0.6 0 0.4 ?.2 tpc 4. typical inl input frequency ?khz 80 65 10 10000 100 sinad ?db 1000 70 75 tpc 5. sinad vs. input tone (ad8021 input circuit) input frequency ?khz ?0 100 1000 thd ?db ?0 ?0 ?00 ?0 10000 ?0 ?0 100 10 0 51 200 tpc 6. thd vs. input tone for different input resistances
rev. 0 C8C AD7484 frequency ?khz 0 10 100 psrr ?db ?0 ?0 ?0 ?0 1000 ?0 ?0 ?0 ?0 100mv p-p sine wave supply pins tpc 7. psrr without decoupling temperature ? c 0.0004 ?5 ?5 5 35 95 125 refout ?v ?.0004 ?.0008 ?.0012 ?.0016 ?.0020 0 65 tpc 8. reference error 220 bias vo ltag e 1 2 3 4 5 6 7 8 ad8021 50 ac signal 220 10pf ? s +v s + v in 10pf figure 2. analog input circuit used for 1 mhz input tone 1 2 3 4 5 6 7 8 ad829 1k 1k 100 ac signal bias vo ltag e 150 220pf ? s +v s + v in figure 1. analog input circuit used for 10 khz input tone figure 1 shows the analog input circuit used to obtain the data for the fft plot shown in tpc 1. the circuit uses an analog devices ad829 op amp as the input buffer. a bipolar analog signal is applied as shown and biased up with a stable, low noise dc voltage connected to the labeled terminal shown. a 220 pf compensation capacitor is connected between pin 5 of the ad829 and the analog ground plane. the ad829 is supplied with +12 v and C 12 v supplies. the supply pins are decoupled as close to the device as possible, with both a 0.1 f and 10 f capacitor connected to each pin. in each case, the 0.1 f capacitor should be the closer of the two caps to the device. more information on the ad829 is available on the analog devices website. for higher input bandwidth applications, analog devices ad8021 op amp (also available as a dual ad8022) is the recommended choice to drive the AD7484. figure 2 shows the analog input circuit used to obtain the data for the fft plot shown in tpc 2. a bipolar analog signal is applied to the terminal shown and biased up with a stable, low noise dc voltage connected as shown. a 10 pf compen- sation capacitor is connected between pin 5 of the ad8021 and the negative supply. as with the previous circuit, the ad8021 is supplied with +12 v and C 12 v supplies. the supply pins are decoupled as close to the device as possible, with both a 0.1 f and 10 f capacitor connected to each pin. in each case, the 0.1 f capacitor should be the closer of the two caps to the device. the ad8021 logic reference pin is tied to analog ground, and the disable pin is tied to the positive supply as shown. detailed information on the ad8021 is available on the analog devices website.
rev. 0 AD7484 C9C circuit description converter operation the AD7484 is a 14-bit algorithmic successive-approximation analog-to-digital converter based around a capacitive dac. it pro- vides the user with track -and- hold, reference, an a/d converter, and versatile interface logic functions on a single chip. the normal analog input signal range that the AD7484 can convert is 0 v to 2.5 v. by using the offset and overrange features on the adc, the AD7484 can convert analog input signals from C 200 mv to +2.7 v while operating from a single 5 v supply. the part requires a 2.5 v reference, which can be provided from the part s own internal reference or an external reference source. figure 3 shows a very simplified schematic of the adc. the control logic, sar, and capacitive dac are used to add and subtract fixed amounts of charge from the sampling capacitor to bring the comparator back to a balanced condition. capacitive dac switches v in v ref sar control logic control inputs output data 14-bit parallel comparator figure 3. simplified block diagram of AD7484 conversion is initiated on the AD7484 by pulsing the convst input. on the falling edge of convst , the track-and-hold goes from track mode to hold mode and the conversion sequence is started. conversion time for the part is 300 ns. figure 4 shows the adc during conversion. when conversion starts, sw2 will open and sw1 will move to position b, causing the com- parator to become unbalanced. the adc then runs through its successive approximation routine and brings the comparator back into a balanced condition. when the comparator is rebalanced, the conversion result is available in the sar register. capacitive dac comparator control logic + sw1 sw2 a gnd v in a b figure 4. adc conversion phase at the end of conversion, the track-and-hold returns to track mode and the acquisition time begins. the track-and-hold acquisi- tion time is 40 ns. figure 5 shows the adc during its acquisition phase. sw2 is closed and sw1 is in position a. the comparator is held in a balanced condition and the sampling capacitor acquires the signal on v in . capacitive dac comparator control logic + sw1 sw2 a gnd v in a b figure 5. adc acquisition phase adc transfer function the output coding of the AD7484 is straight binary. the de signed code transitions occur midway between the successive integer lsb values (i.e., 1/2 lsb, 3/2 lsb, and so on). the lsb size is v ref /16384. the nominal transfer characteristic for the AD7484 is shown in figure 6. this transfer characteristic may be shifted as detailed in the offset/overrange section. 000...000 0v adc code analog input 111...111 000...001 000...010 111...110 111...000 011...111 0.5lsb +v ref ?.5lsb 1lsb = v ref /16384 figure 6. AD7484 transfer characteristic power saving the AD7484 uses advanced design techniques to achieve very low power dissipation at high throughput rates. in addition to this, the AD7484 features two power saving modes, nap and standby. these modes are selected by bringing either the nap or stby pin to a logic high, respectively. when operating the AD7484 in normal fully powered mode, the current consumption is 18 ma during conversion and the quies- cent current is 12 ma. operating at a throughput rate of 1 msps, the conversion time of 300 ns contributes 27 mw to the overall power dissipation. 300 1 5 18 27 ns s v ma mw / () () = for the remaining 700 ns of the cycle, the AD7484 dissipates 42 mw of power. 700 1 5 12 42 ns s v ma mw / () () = thus, the power dissipated during each cycle is: 27 42 69 mw mw mw +=
rev. 0 C10C AD7484 figure 7 shows the AD7484 conversion sequence operating in normal mode. c onvst busy 300 ns 1 s 700 ns figure 7. normal mode power dissipation in nap mode, almost all of the internal circuitry is powered down. in this mode, the power dissipation of the AD7484 is reduced to 2.5 mw. when exiting nap mode, a minimum of 300 ns when using an external reference must be waited before initiating a conversion. this is necessary to allow the internal circuitry to settle after power-up and for the track-and-hold to properly acquire the analog input signal. the internal reference cannot be used in conjunction with the nap mode. if the AD7484 is put into nap mode after each conversion, the average power dissipation will be reduced, but the throughput rate will be limited by the power-up time. using the AD7484 with a throughput rate of 500 ksps while placing the part in nap mode after each conversion would result in average power dissi- pation as follows: the power-up phase contributes: 300 2 5 12 9 ns s v ma mw / ( ) ( ) = the conversion phase contributes: 300 2 5 18 13 5 ns s v ma mw /. () () = while in nap mode for the rest of the cycle, the AD7484 dissipates only 1.75 mw of power. 1400 2 5 0 5 1 75 ns s v ma mw /.. () () = thus, the power dissipated during each cycle is: 9135175 2425 mw . mw . mw mw ++ = . figure 8 shows the AD7484 conversion sequence if putting the part into nap mode after each conversion. c onvst 600ns nap busy 300ns 1400ns 2 s figure 8. nap mode power dissipation figures 9 and 10 show a typical graphical representation of power versus throughput for the AD7484 when in normal and nap modes, respectively. throughput ?ksps 60 0 3000 power ?mw 500 1000 1500 2000 2500 65 70 75 80 85 90 figure 9. normal mode, power vs. throughput throughput ?ksps 0 0 2000 250 power ?mw 750 1250 1500 1750 10 500 1000 20 30 40 50 60 70 80 90 figure 10. nap mode, power vs. throughput in standby mode, all the internal circuitry is powered down and the power consumption of the AD7484 is reduced to 10 w. the power-up time necessary before a conversion can be initiated is longer because more of the internal circuitry has been powered down. in using the internal reference of the AD7484, the adc must be brought out of standby mode 500 ms before a conver- sion is initiated. initiating a conversion before the required power-up time has elapsed will result in incorrect conversion data. if an external reference source is used and kept powered up while the AD7484 is in standby mode, the power-up time required will be reduced to 80 s.
rev. 0 AD7484 C11C offset/overrange the AD7484 provides a 8% overrange capability as well as a programmable offset register. the overrange capability is achieved by the use of a 15th bit (d14) and the clip input. if the clip input is at logic high and the contents of the offset register are zero, then the AD7484 operates as a normal 14-bit adc. if the input voltage is greater than the full-scale voltage, the data output from the adc will be all 1s. similarly, if the input voltage is lower than the zero-scale voltage, the data output from the adc will be all 0s. in this case, d14 acts as an overrange indica tor. it is set to 1 if the analog input voltage is outside the nominal 0 v to 2.5 v range. if the offset register contains any value other than 0, the contents of the register are added to the sar result at the end of conver- sion. this has the effect of shifting the transfer function of the adc as shown in figure 11 and figure 12. however, it should be noted that with the clip input set to logic high, the maximum and minimum codes that the AD7484 will output will be 0x3fff and 0x0000, respectively. further details are given in table i and table ii. figure 11 shows the effect of writing a positive value to the offset register. if, for example, the contents of the offset register con- tained the value 1024, then the value of the analog input voltage for which the adc would transition from reading all 0s to 000...001 (the bottom reference point) would be: 05 1024 156 326 . CC . lsb lsb mv () = the analog input voltage for which the adc would read full-scale (0x3fff) in this example would be: 25 15 1024 2 34352 . C . C . v lsb lsb v () = analog input 0v 1lsb = v ref /16384 0.5lsb ?ffset 000...000 adc code 111...111 000...001 000...010 111...110 111...000 011...111 +v ref ?1.5lsb ?ffset figure 11. transfer characteristic with positive offset the effect of writing a negative value to the offset register is shown in figure 12. if a value of C 512 was written to the offset register, the bottom end reference point would now occur at: 05 512 78 20 . CC . lsb lsb mv () = following this, the analog input voltage needed to produce a full-scale (0x3fff) result from the adc would now be: 25 15 512 2 5779 . C . CC . v lsb lsb v () = 000...000 0v adc code analog input 111...111 000...001 000...010 111...110 111...000 011...111 0.5lsb ?ffset +v ref ?1.5lsb ?ffset 1lsb = v ref /16384 figure 12. transfer characteristic with negative offset table i shows the expected adc result for a given analog input voltage with different offset values and with clip tied to logic high. the combined advantages of the offset and overrange features of the AD7484 are shown clearly in table ii. it shows the same range of analog input and offset values as table i but with the clipping feature disabled. table i. clipping enabled (clip = 1) offset ?12 0 +1024 vin adc data, d[0:13] d14 C 200 mv 0 0 0 1 1 1 C 156.3 mv 0 0 0 1 1 0 0 v 0 0 1024 1 0 0 +78.2 mv 0 512 1536 0 0 0 +2.3435 v 14846 15358 16383 0 0 0 +2.5 v 15871 16383 16383 0 0 1 +2.5779 v 16383 16383 16383 0 1 1 +2.7 v 16383 16383 16383 1 1 1 table ii. clipping disabled (clip = 0) offset ?12 0 +1024 vin adc data, d[0:14] C 200 mv C 1823 C 1311 C 287 C 156.3 mv C 1536 C 1024 0 0 v C 512 0 1024 +78.2 mv 0 512 1536 +2.3435 v 14846 15358 16382 +2.5 v 15872 16384 17408 +2.5779 v 16383 16895 17919 +2.7 v 17183 17695 18719 values from C 1310 to +1310 may be written to the offset regis ter. these values correspond to an offset of 200 mv. a write to the offset register is performed by writing a 13-bit word to the part as detailed in the parallel interface section. the 12 lsbs of the 15- bit word contain the offset value, while the 3 msbs must be set to 0. failure to write zeros to the 3 msbs may result in the in correct operation of the device.
rev. 0 C12C AD7484 parallel interface the AD7484 features two parallel interfacing modes. these modes are selected by the mode pins as detailed in table iii. table iii. operating modes mode 2 mode 1 do not use 0 0 parallel mode 1 0 1 parallel mode 2 1 0 do not use 1 1 in parallel mode 1, the data in the output register is updated on the rising edge of busy at the end of a conversion and is avail- able for reading almost immediately afterwards. using this mode, throughput rates of up to 2.5 msps can be achieved. this mode should be used if the conversion data is required immediately after the conversion has completed. an example where this may be of use is if the AD7484 was operating at much lower throughput rates in conjunction with nap mode (for power-saving reasons), and the input signal was being compared with set limits within the dsp or other controller. if the limits were exceeded, the adc would then be brought immediately into full power operation and commence sampling at full speed. figure 17 shows a timing diagram for the AD7484 operating in parallel mode 1 with both cs and rd tied low. in parallel mode 2, the data in the output register is not updated until the next falling edge of convst . this mode could be used where a single sample delay is not vital to the system operation and conversion speeds of greater than 2.5 msps are desired. this may occur, for example, in a system where a large amount of samples are taken at high speed before a fast fourier transform is performed for frequency analysis of the input signal. figure 18 shows a timing diagram for the AD7484 operating in parallel mode 2 with both cs and rd tied low. data must not be read from the AD7484 while a conversion is taking place. for this reason, if operating the AD7484 at throughput speeds greater than 2.5 msps, it will be necessary to tie both the cs and rd pins on the AD7484 low and use a buffer on the data lines. this situation may also arise in the case where a read operation cannot be completed in the time after the end of one conversion and the start of the quiet period before the next conversion. the maximum slew rate at the input of the adc should be limited to 500v/ s while busy is low to avoid corrupting the ongoing conversion. in any multiplexed application where the channel is switched during conversion, this should happen as early as possible after the busy falling edge. reading data from the AD7484 data is read from the part via a 15-bit parallel databus with the standard cs and rd signals. the cs and rd signals are internally gated to enable the conversion result onto the databus. the data lines d0 to d14 leave their high impedance state when both cs and rd are logic low. therefore, cs may be permanently tied logic low if required, and the rd signal used to access the conver- sion result. figure 15 shows a timing specification called t quiet . this is the amount of time that should be left after any databus activity before the next conversion is initiated. writing to the AD7484 the AD7484 features a user-accessible offset register. this allows the bottom of the transfer function to be shifted by 200 mv. this feature is explained in more detail in the offset/overrange section. to write to the offset register, a 15-bit word is written to the AD7484 with the 12 lsbs containing the offset value in two s complement format. the 3 msbs must be set to 0. the offset value must be within the range C 1310 to +1310, corresponding to an offset from C 200 mv to +200 mv. the value written to the offset register is stored and used until power is removed from the device, or the device is reset. the value stored may be updated at any time between conversions by another write to the device. table iv shows some examples of offset register values and their effective offset voltage. figure 16 shows a timing diagram for writing to the AD7484. table iv. offset register examples d11?0 (two? offset code (dec) d14?12 complement) (mv) C 1310 000 101011100010 C 200 C 512 000 111000000000 C 78.12 +256 000 000100000000 +39.06 +1310 000 010100011110 +200 driving the convst pin to achieve the specified performance from the AD7484, the convst pin must be driven from a low-jitter source. since the falling edge on the convst pin determines the sampling in stant, any jitter that may exist on this edge will appear as noise when the analog input signal contains high frequency components. the relationship between the analog input frequency ( f in ), timing jitter ( t j ), and resulting snr is given by the equation: snr db t itter j j in 1 2f () = () 10 2 log as an example, if the desired snr due to jitter was 100 db with a maximum full-scale analog input frequency of 1.5 mhz, ignor- ing all other noise sources, the result is an allowable jitter on the convst falling edge of 1.06 ps. for a 14-bit converter (ideal snr = 86.04 db), the allowable jitter will be greater than the figure given above, but due consideration must be given to the d esign of the convst circuitry to achieve 14-bit perfor- mance with large analog input frequencies.
rev. 0 AD7484 C13C typical connection figure 13 shows a typical connection diagram for the AD7484 operating in parallel mode 1. conversion is initiated by a falling edge on convst . once convst goes low, the busy signal goes low, and at the end of conversion, the rising edge of busy is used to activate an interrupt service routine. the cs and rd lines are then activated to read the 14 data bits (15 bits if using the overrange feature). in figure 13, the v drive pin is tied to dv dd , which results in logic output levels being either 0 v or dv dd . the voltage ap plied to v drive controls the voltage value of the output logic signals. for example, if dv dd is supplied by a 5 v supply and v drive by a 3 v supply, the logic output levels would be either 0 v or 3 v. this feature allows the AD7484 to interface to 3 v devices while still enabling the adc to process signals at a 5 v supply. c/ p reset p arallel interface mode1 mode2 write clip nap stby d0?12 cs convst rd busy c bias refsel refin refout vin ad7482 adm809 v drive dv dd av dd 0.1 f digital supply 4.75v?.25v 10 f 1nf + 0.1 f 0.1 f + 47 f analog supply 4.75v?.25v 0v to 2.5v 1nf 0.47 f 0.47 f ad780 2.5v reference figure 13. typical connection diagram board layout and grounding to obtain optimum performance from the AD7484, it is recom- mended that a printed circuit board with a minimum of three layers be used. one of these layers, preferably the middle layer, should be as complete a ground plane as possible to give the best shielding. the board should be designed in such a way that the analog and digital circuitry is separated and confined to certain areas of the board. this practice, along with avoiding running digital and analog lines close together, should help to avoid coupling digital noise onto analog lines. the power supply lines to the AD7484 should be approximately 3 mm wide to provide low impedance paths and reduce the effects of glitches on the power supply lines. it is vital that g ood decoupling is also present. a combination of ferrites and decoupling capacitors should be used as shown in figure 13. the decoupling capacitors should be as close to the supply pins as possible. this is made easier by the use of multilayer boards. the signal traces from the AD7484 pins can be run on the top layer while the decoupling capacitors and ferrites can be mounted on the bottom layer where the power traces exist. the ground plane between the top and bottom planes provide excellent shielding. figures 14a to 14e show a sample layout of the board area immediately surrounding the AD7484. pin 1 is the bottom left corner of the device. figure 14a shows the top layer where the AD7484 is mounted with vias to the bottom routing layer high- lighted. figure 14b shows the bottom layer where the power routing is with the same vias highlighted. figure 14c shows the bottom layer silkscreen where the decoupling components are soldered directly beneath the device. figure 14d shows the silkscreen overlaid on the solder pads for the decoupling compo- nents, and figure 14e shows the top and bottom routing layers overlaid. the black area in each figure indicates the ground plane present on the middle layer. c1 C 6: 100 nf, c7 C 8: 470 nf, c9: 1 nf l1 C 4: meggit-sigma chip ferrite beads (bmb2a0600rs2) figure 14a figure 14c figure 14b figure 14d figure 14e
rev. 0 C14C AD7484 busy cs rd c onvst d[14:0] t 1 t 2 t 4 data valid t 3 t 7 t q uiet t conv t acq t 14 t 15 t 8 figure 15. parallel mode read cycle convst cs rd d[14:0] offset data t 12 t 13 t 9 t 10 t 11 write figure 16. parallel mode write cycle
rev. 0 AD7484 C15C busy c onvst d[14:0] t 1 t 6 data n? data n t conv n+1 n t 2 figure 17. parallel mode 1 read cycle busy c onvst d[14:0] t 1 t 5 data n? data n t conv n n+1 t 2 figure 18. parallel mode 2 read cycle
c02642C0C8/02(0) printed in u.s.a. C16C AD7484 outline dimensions 48-lead plastic quad flatpack [lqfp] (st-48) dimensions shown in millimeters top view (pins down) 1 12 13 25 24 36 37 48 0.27 0.22 0.17 0.50 bsc 7.00 bsc sq seating plane 1.60 max 0.75 0.60 0.45 view a 7 3.5 0 0.20 0.09 1.45 1.40 1.35 0.15 0.05 0.08 max coplanarity view a rotated 90 ccw pin 1 indicator 9.00 bsc sq compliant to jedec standards ms-026bbc

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