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u4065b rev. a4, 06-mar-01 1 (23) fm receiver description the ic u4065b is a bipolar integrated fm-frontend circuit. it contains a mixer, an oscillator, two if preamplifiers and an unique interference sensor. the device is designed for high performance car radio and home receiver applications. features all frontend functions of a high performance fm- receiver, except the rf preamplifier, are integrated improved dynamic range by high current double balanced mixer design and a new agc conception with 3 loops on chip improved blocking and intermod behavior by use of an unique ainterferenceo sensor controlling the agc easy cascading of three if filters (ceramic) by use of two on-chip if preamplifiers on-chip control functions are available for system gain adjust (db linear vs. dc current) low noise lo design esd protected block diagram v s 22 1 11 9 810 6 17 13 3 5 7 4 21 18 19 16 15 14 23 24 + if bpf if bpf if bpf if out p if 2 if 1 if gain adjust v s voltage reg. if bpf ant inter- ference mixer mixer rf pin at t rf tank v tune rf tank local oscill. if tank lo output v ref = 4 v 20 2 lo tank agc adjust agc level v s v s 12 d.n.c. agc (wide band) wide band & if i f & detector interference 94 8768
u4065b rev. a4, 06-mar-01 2 (23) pin description pin symbol function 1 lobuff buffered local oscillator output 2 gnd1 ground of the second if ampli- fier 3 if2out output of the second if ampli- fier 4 gainif1 gain control of the first if amplifier 5 if2in input of the second if amplifier 6 vs supply voltage 7 if1out output of the first if amplifier 8 gnd2 ground 9 imifin input of the amplifier for the im-sensor 10 agcout output of the automatic gain control 11 immixout output of the intermodulation mixer 12 d.n.c. do not connect pin symbol function 13 agcwb threshold adjustment of the wideband agc 14 gnd3 mixer ground 15 mixin1 input 1 of the double balanced mixer 16 mixin2 input 2 of the double balanced mixer 17 vref reference voltage output 18 mixout1 mixer output 1 19 mixout2 mixer output 2 20 gnd4 ground of the first if amplifier 21 if1in input of the first amplifier 22 gnd5 oscillator ground 23 loe local oscillator (emitter) 24 lob local oscillator (base) lobuff 23 50 1 1 v esd + 94 8769 buffered local oscillator output: it drives the fm-input of the pll circuit (for example u428xbm-family). the typical parallel output resistance at 100 mhz is 70 , the parallel output capacitance is about 10 pf. when using an external load of 500 / 10 pf, the oscillator swing is about 100 mv. the second harmonic of the oscillator frequency is less than 15 dbc. gnd1 esd 2 8 94 8770 ground of the second if amplifier: there is no internal connection to the other ground pins.
u4065b rev. a4, 06-mar-01 3 (23) if2out 3 esd v s v ref 94 8771 output of the second if amplifier: the parallel output capacitance to ground is about 7 pf. the external load resistance is to connect to v s . the dc current into the pin is typically 3 ma. note: supply voltage v s has to be protected against if-distortion gainif1 17 4 esd v ref 2 k 94 8772 gain control of the first if amplifier: the gain of the first if amplifier can be adjusted by a re- sistor to ground. this is useful for example to com- pensate the insertion loss tolerances of the ceramic bpf's. please ensure that the output current of the pin does not exceed 150 a in any case. linear increasing in the cur- rent out of gainif1 effects db linear increasing of the gain (0.15 db/ a). i4 = 0 g= gmin = 2 db i4 = 140 a g = gmax = 22 db if2in esd 5 v ref 94 8773 input of the second if amplifier: the parallel input resistance is 330 . the parallel input capacitance is about 12 pf. no dc current is allowed. to avoid overload of this stage an internal detector watches the input level and causes current at the agcout pin. if1out esd 330 7 v s 94 8774 output of the first if amplifier: the parallel output resistance is 330 which allows the use of a standard ceramic bpf. the parallel output capa- citance is about 7 pf. the dc voltage at the pin is 0.5 v less than v s . imifin 9 esd 94 8775 input of the if amplifier for the im-sensor: the parallel input resistance is 330 . the amplifier is ex- tremely sensitive to ac signals. a few hundred v of if-signal at this pin will cause current at the agc output. therefore pay attention when connecting the standard ce- ramic filter used between imout and this pin. the reference point of the filter has to be free of any ac signal. please avoid dc current at this pin.
u4065b rev. a4, 06-mar-01 4 (23) agcout 10 1 k 1 v esd 94 8776 output of the automatic gain control: the agc output is an open collector output. the current of the pin diode is this current multiplied by the current gain of the external pnp transistor. the dc voltage at the pin may vary from 2 v to v s , therefore you can easily use this pin as an indicator of the agc regulation state. immixout esd 300 v s 1 v 11 94 8777 output of the intermodulation mixer: the parallel output resistance is 330 which allows the use of a standard ceramic bpf without any further match- ing network. please ensure that the ground-pin of the filter is free of ac signals. agcwb 25 k 32 k esd 13 v ref 94 8778 threshold adjustment of the wideband agc: the threshold of the wideband agc can be adjusted by an external resistor to ground. the setting range is 10 db. for minimum blocking this pin is connected to ground. in order to set the threshold to smaller levels the resistance value should be up to a few hundred k . mixin1 2.5 k 15 esd v ref 94 8779 input 1 of the double balanced mixer: the parallel input resistance is 1.2 k . the parallel input capacitance is about 9 pf. when using the mixer unbal- anced this pin is to be grounded for rf-signals by an external capacitance of a few nf. dc current is not allowed. mixin2 2.5 k 16 esd v ref 94 8780 input 2 of the double balanced mixer: the parallel input resistance is 1.6 k . the parallel input capacitance is about 7 pf. the double sideband noise fig- ure of the unbalanced mixer is about 7 db. in the balanced case the noise figure will be reduced by about 0.8 db. vref 94 8781 4.6 v 200 esd v s 17 reference voltage: the internal temperature compensated reference voltage is 3.9 v. it is used as bias voltage for most blocks, so the electrical characteristics of the u4065b are widely inde- pendent of the supply voltage. the internal output resistance of the reference voltage is less than 10 . to avoid internal coupling across this pin external capacitors are required. the maximum output current is i ref = 5 ma.
u4065b rev. a4, 06-mar-01 5 (23) mixout1, mixout2 18 esd 94 8782 19 mixer output 1, 2: the mixer output is an open collector of a bipolar transis- tor. the minimum voltage at this pins is 5 v (v s -voltage swing). the dc current into this pins is typically 9 ma. good lo- and rf suppression at the mixer output can be achieved by symmetrical load conditions at the pins mix- out1 and mixout2. if1in 21 330 v ref esd 94 8784 input of the first if amplifier: the typical input resistance is 330 . the dc voltage is nearly the same one as the reference voltage. please avoid dc current at this pin. loe 23 esd 94 8785 emitter of the local oscillator: an external capacitor is connected between loe and ground. the ground pin of this capacitor is to connect to the pin gnd5. gnd5 is the chip internal ground of the local oscillator. lob 24 esd 94 8786 base of the local oscillator: the tank of the local oscillator is connected at pin lob. the ground pin of this tank is to connect to the pin gnd5. gnd5 is the chip internal ground into pin 24 of the local oscillator. the resonant resistance of the tank should be about 250 . minimum q of the unloaded tank is 50.
u4065b rev. a4, 06-mar-01 6 (23) functional description the u4065b fm-frontend ic is the dedicated solution for high end car radios. a new design philosophy enables to build up tuners with superior behavior. this philosophy is based on the fact that the sensitivity of state of the art designs is at the physical border and cannot be enhanced any more. on the other hand, the spectral power density in the fm-band increases. an improvement of reception can only be achieved by increasing the dynamic range of the receiver. this description is to give the designer an introduction to get familiar with this new product and its philosophy. 1. the signal path the u4065b offers the complete signal path of an fm- frontend including a highly linear mixer and two if preamplifiers. the mixer is a double balanced high cur- rent gilbert cell. a high transit frequency of the internal transistors enables the use of the emitter grounded circuit with its favorable noise behavior. the full balanced out- put offers lo carrier reduction. the following if preamplifier has a db-linear gain adjust- ment by dc means. thus different ceramic filter losses can be compensated and the overall tuner gain can be adapted to the individual requirements. the low noise design sup- presses post stage noise in the signal path. input- and output resistance is 330 to support standard ceramic fil- ters. this was achieved without feedback, which would cause different input impedances when varying the output impedance. the second if preamplifier enables the use of three ce- ramic filters with real 330 input- and output termination. feedthrough of signals is kept low. the high level of output compression is necessary to keep up a high dynamic range. beneath the signal path the local oscillator part and the agc signal generation can be found on chip. the local oscillator uses the collector grounded colpitts type. a low phase noise is achieved with this access. a mutual cou- pling in the oscillator coil is not necessary. 2. the agc concept special care was taken to design a unique agc concept. it offers 3 agc loops for different kinds of reception conditions. the most important loop is the interference sensor part. in today's high end car radios, the fm agc is state of the art. it is necessary to reduce the influence of 3rd and higher order intermodulation to sustain reception in the presence of strong signals in the band. on one hand, it makes a sense to reduce the desired signal level by agc as few as possible to keep up stereo reception, on the other hand two or more strong out of channel signals may inter- fere and generate an intermodulation signal on the desired frequency. by introducing input attenuation, the level of the intermod signal decreases by a higher order, whereas the level of the desired signal shows only a linear depen- dency on the input attenuation. therefore input attenuation by pin diodes may keep up reception in the presence of strong signals. the standard solution to generate the pin diode current is to pick up the rf-signal in front of the mixer. because the bandwidth at that point is about 1.5 mhz, this is called wideband agc. the threshold of agc start is a critical parameter. a low threshold does not allow any intermo- dulation but has the disadvantage of blocking if there is only one strong station on the band or if the intermod sig- nals do not cover the desired channel. a higher agc threshold may tolerate a certain ground floor of intermo- dulation. this avoids blocking, but it has the disadvantage, that no reception is possible, if the interfer- ing signals do generate an intermod signal inside the desired channel. this contradiction could not be over- come in the past. with the new u4065b ic, a unique access to this problem appears. this product has an interference sensor on chip. thus an input signal attenuation is only performed, if the interfering signals do generate an intermod signal inside the desired channel. if they do not, the still existing wide- band agc is yet active but at up to 20 db higher levels. the optimum agc state is always generated. the figures 1 to 4 illustrate the situation. in figure 1 the agc threshold of a standard tuner is high to avoid block- ing. but then the intermod signal suppresses the desired signal. the interference sensor of the u4065b takes care that in this case the agc threshold is kept low as illus- trated in figure 2. in figure 3 the situation is vice versa. the agc threshold of a standard tuner is kept low to avoid intermod prob- lems. but then blocking makes the desired signal level drop below the necessary stereo level. in this case, the higher wideband agc level of the u4065b enables per- fect stereo reception. by principle, this interference sensor is an element with a third order characteristic. for input levels of zero, the output level is zero, too. with increasing input level, the output level is increased with the power of three, thus pre- ferring intermod signals compared to linear signals. at the same time, a down conversion to the if level of 10.7 mhz is performed. if a corresponding 10.7 mhz if filter selects the intermod signals, an output is only gener- ated, if an intermod signal inside the 10.7 mhz channel is present.
u4065b rev. a4, 06-mar-01 7 (23) the circuit blocks interference sensor and if & detector build up a second if chain. in an fm system, the max deviation of a 3rd order intermod signal is the triple max deviation of the desired signal. therefore the ceramic if bpf between pin 11 and pin 9 may be a large bandwidth type. this external part is the only additional amount for this unique feature. a further narrow band agc avoids overriding the second if amplifier. the amplitude information of the channel is not compressed in order to maintain multipath detection in the if part of the receiver. ???????????? ???????????? ???????????? stereo-level interfering signals intermod signal noise floor desired signal level frequency desired frequency intermod signal 94 8820 figure 1 a high agc threshold causes the intermod signal to suppress the desired signal ????????????? ????????????? ????????????? stereo-level interfering signals intermod signal noise floor desired signal level frequency desired frequency intermod signal 94 8821 figure 2 the correct agc threshold of the u4065b provides optimum reception ???????????? ???????????? stereo-level strong signal noise floor desired signal level frequency desired frequency 94 8822 figure 3 a low agc threshold causes the blocking signal to suppress the desired signal ????????????? ????????????? stereo-level noise floor desired signal level frequency desired frequency strong signal 94 8823 figure 4 the correct agc threshold of the u4065b provides optimum reception
u4065b rev. a4, 06-mar-01 8 (23) absolute maximum ratings reference point is ground (pins 2, 8, 14, 20 and 22) parameters symbol value unit supply voltage v s 10 v power dissipation at t amb = 85 c p tot 470 mw junction temperature t j 125 c ambient temperature range t amb 30 to + 85 c storage temperature range t stg 50 to + 125 c electrostatic handling: human body model (hbm), all i/o pins tested against the supply pins. v esd 2000 v thermal resistance parameters symbol maximum unit thermal resistance r thja 90 k/w electrical characteristics v s = 8.0 v, f rf = 98 mhz, f osc 108.7 mhz, f if = f osc f rf = 10.7 mhz reference point ground (pins 2, 8, 14, 20 and 22),t amb = 25 c, unless otherwise specified parameters test conditions / pins symbol min. typ. max. unit supply voltage pins 3, 6, 10, 18 and 19 v s 7 8 10 v supply current pins 3+6+10+18+19 i tot 37 47 ma oscillator (gnd5 has to be connected to external oscillator components) oscillator voltage r g24 = 220 , unloaded q of l osc = 70, r l1 = 520 pin 24 pin 23 pin 1 v lob v loe v lobuff 70 160 100 90 220 mv harmonics pin 1 15 dbc output resistance pin 1 r lo 70 voltage gain between pins 1 and 23 0.9 mixer (gnd3 has to be separated from gnd1, gnd2 and gnd4) conversion power gain source impedance: g c 5 7 10 db 3rd order input intercept source impedance: r g15,16 = 200 ldi d ip 3 4 6 14 dbm conversion transconductance , load impedance: r l18 19 = 200 g c 8 ma/v noise figure r l18,19 = 200 nf dsb 7 db input resistance to ground pin 15 r ignd15 1.2 k input capacitance to ground pin 15 f = 100 mhz c ignd15 9 pf input resistance to ground pin 16 r ignd16 1.6 k input capacitance to ground pin 16 f = 100 mhz c ignd16 7 pf input-input resistance between pin 15 and pin 16 r ii15,16 1.6 k input-input capacitance between pin 15 and pin 16 c ii15,16 5 pf output capacitance to gnd pin 18 and pin 19 c ignd18,19 9 pf first if preamplifier (if 1) gain control deviation by i 4 pin 4 17 20 24 db gain control slope pin 4 dg if1 /di 4 0.15 db/ a
u4065b rev. a4, 06-mar-01 9 (23) electrical characteristics (continued) v s = 8.0 v, f rf = 98 mhz, f osc 108.7 mhz, f if = f osc f rf = 10.7 mhz reference point ground (pins 2, 8, 14, 20 and 22),t amb = 25 c, unless otherwise specified parameters test conditions / pins symbol min. typ. max. unit external control current to ground at g min at g nom at g max i 4min i 4nom i 4max 0 70 140 a power gain at i 4min at i 4nom at i 4max between pins 21 and 7 source impedance: g min g nom g max 2.5 11 19 2 12 22 2.5 16 28 db noise figure at g max at g nom at g min source impedance: r g21 = 200 , load impedance: r l7 =200 nf min nf nom nf max 7 9 15 db temperature coefficient of the gain at g nom tknom +0.045 db/k 1 db compression at g nom pin 7 v cnom 70 mv 3 db cutoff freq. at g nom pin 7 f cnom 50 mhz input resistance pin 21 r iif1 270 330 400 input capacitance pin 21 f = 10 mhz c iif1 5 pf output resistance pin 7 r oif1 270 330 400 output capacitance pin 7 f = 10 mhz c oif1 7 pf second if preamplifier (if 2) power gain etween pins 5 and 3 source impedance: r g5 = 200 load impedance: r l3 =200 g if2 15 18 19 db noise figure nf if2 7 db 1 db compression pin 3 v comp 500 mv 3 db cutoff frequency pin 3 f c 50 mhz parallel input resistance pin 5 r iif2 270 330 400 parallel input capacitance pin 5 f = 10 mhz c iif2 12 pf parallel output resistance pin 3 r oif2 50 k parallel output capacitance pin 3 f = 10 mhz c oif2 7 pf voltage regulator regulated voltage pin 17 v ref 3.7 3.9 4.9 v maximum output current pin 17 i ref 5 ma internal differential resistance, dc 17 /di 17 when i 17 = 0 pin 17 r d17 7 50 power supply suppression f = 50 hz, pin 17 psrr 36 50 db agc input voltage thresholds (agc threshold current is 10 a at pin 10) if2 input pin 5 v thif2 85 86 92 db v if & detector pin 9 v thifd 42 43 48 db v mixer input level of wideband sensor between pins 15 and 16 f irf = 100 mhz v at pin 13 = 0 v i through pin 13 = 0 a v thwb1 v thwb2 95 85 98 87 100 90 db v db v
u4065b rev. a4, 06-mar-01 10 (23) test circuit if 1 if 2 agc block mixer interference mixer amplifier local oscillator 21 50 1 5 62 4.7n 4 20 7 52 3 10 i10 v 1 5 6 2 vs vo if 50 1 5 6 2 4.7n 4.7n 18 19 14 15 16 24 23 50 vi rf losc 47p 33p 12 470p rl1 vlobuff flobuff 1 22 11 1 5 6 2 vo if 50 1 5 6 2 50 vi if 4.7n 1 9 17 6 vs 1 5 6 2 vs 50 1 5 6 2 1 5 6 2 voltage regulator 4.7n 50 4.7n 50 vi if vo if vo if gain if 1 i18,19 8 i6 13 i3 rg15,16 rl18,19 rg21 i4 rl7 rg5 rl3 r13 rg9 rg11 rlobuff 1 5 6 2 0 0 4 50 200 z/ohm rf transformers mcl type tmo 4 1 vi if 0 to 140 a rg24 94 8829 vref = 4 v il = 0.7 db 8 p fosc cosc agc adjust (wide band) i13 4.7n interference
u4065b rev. a4, 06-mar-01 11 (23) local oscillator oscillator oscillator output buffer 24 23 v osc24 v osc1 , f osc 520 1 r g24 f osc t amb 47p 33p local 94 9410 free running oscillator frequency f osc 110 mhz, v osc24 = 160 mv, r g24 =220 , q l = 70 0 20 40 60 80 100 120 140 160 180 30 10 10 30 50 70 90 v ( mv ) osc1 t amb ( c ) 94 9411 oscillator swing versus temperature
u4065b rev. a4, 06-mar-01 12 (23) mixer f osc = 110.7 mhz, v osc24 160 mv, f if = 10.7 mhz 1 5 6 2 50 1 5 6 2 50 t amb il1 vo if mixer 18 19 14 15 v s f osc oscillator 47p r g24 24 23 local f rf1 f rf2 2vi rf1 2vi rf2 22p il2 conversion power gain g c = 20 log (vo if /vi rf ) + il1 (db) + il2 (db) il1, il2 insertion loss of the rf transformers 94 9412 0 20 40 60 80 100 120 0 20406080100120 vo ( db v ) vi rf1 , vi rf2 ( db v ) 94 9413 conversion characteristic 3rd order im-characteristic if characteristic of the mixer
u4065b rev. a4, 06-mar-01 13 (23) 0 1 2 3 4 5 6 7 8 30 10 10 30 50 70 90 g ( db ) c t amb ( c ) 94 9414 conversion power gain of the mixer stage versus temperature 8.0 8.3 8.6 8.9 9.2 9.5 9.8 10.1 10.4 10.7 11.0 30 10 10 30 50 70 90 i , i ( ma ) 18 t amb ( c ) 94 9415 19 current of the mixer stage versus temperature 1 st if preamplifier 1 5 6 2 50 1 5 6 2 50 if 21 7 i4 t amb il1 1 : 2 2 : 1 il2 4 f if vo if r g21 = 200 vi if21 vo if7 v(pin4) r l7 = 200 2vi if power gain g if = 20 log (vo if /vi if ) + il1 (db) + il2 (db) il1, il2 = insertion loss of the rf transformers 94 9416
u4065b rev. a4, 06-mar-01 14 (23) 5 0 5 10 15 20 25 0 20 40 60 80 100 120 140 g ( db ) if1 i 4 ( a ) 94 9417 t = 30 c t = 90 c t = -30 c power gain of the first if amplifier versus i4 10 5 0 5 10 15 20 25 10 20 30 40 50 60 70 80 90 100 g ( db ) if1 f ( mhz ) 94 9418 g max g nom g min power gain of the first if amplifier versus frequency 2.0 2.2 2.4 2.6 2.8 3.0 3.2 3.4 3.6 3.8 0 20 40 60 80 100 120 140 v ( v ) 4 i 4 ( a ) 94 9419 t = 30 c t = 30 c t = 90 c v (pin 4) versus i 4
u4065b rev. a4, 06-mar-01 15 (23) 2 nd if preamplifier 1 5 6 2 50 1 5 6 2 50 if ?? ?? t amb il1 1 : 2 2 : 1 il2 f if vo if r l3 = 200 330 v s 3 vo if3 vi if5 r g5 = 200 5 2vi if power gain g if = 20 log (vo if /vi if ) + il1 (db) + il2 (db) il1; il2 = insertion loss of the rf transformers 94 9420 15.0 15.5 16.0 16.5 17.0 17.5 18.0 18.5 3020100 102030405060708090 g ( db ) if2 t amb ( c ) 94 9421 power gain of the second if amplifier versus tempera- ture 0 2 4 6 8 10 12 14 16 18 20 10 20 30 40 50 60 70 80 90 100 f ( mhz ) 94 9422 g ( db ) if2 power gain of the second if amplifier versus frequency
u4065b rev. a4, 06-mar-01 16 (23) 86.0 86.2 86.4 86.6 86.8 87.0 30 10 10 30 50 70 90 t amb ( c ) 94 9423 threshold ( db v ) agc threshold (i10 = 1 a) of the second if amplifier versus temperature 0.01 0.10 1.00 10.00 100.00 1000.00 10000.00 80 85 90 95 100 105 vi if ( db a ) 94 9424 i ( a ) 1000.00 10000.00 i10 (30 c ) / a i10 (30 c ) / a i10 (90 c ) / a 10 agc characteristic of the second if amplifier input interference sensor (mixer) 1 5 6 2 50 1 5 6 2 50 il1 vo if 15 v s oscillator 11 interference mixer r l11 = 200 2vi rf1 fi rf1 2vi rf2 fi rf2 f lo f if =200 il2 local 16 r g15/16 il1=il2=0.7db 94 9425 test conditions for characteristic vo if versus vi rf1 : f lo = 100 mhz, f rf1 = 89.3 mhz, vi rf2 = 0, f if = f lo f rf1 = 10.7 mhz test conditions for 3rd order im-characteristic vo if versus vi rf1 , vi rf2 : f lo = 100 mhz. f rf1 =89.4 mhz, f rf2 = 89.5 mhz, f if = f lo (2 f rf1 1 f rf2 ) = 10.7 mhz il1, il2 = insertion loss of the rf transformer
u4065b rev. a4, 06-mar-01 17 (23) 0 10 20 30 40 50 60 70 80 90 60 65 70 75 80 85 90 95 100 vi rf ( db v ) 94 9426 vo ( db v ) conversion characteristic 3rd order im-characteristic if characteristic of the interference sensor (mixer) 20 30 40 50 60 70 80 70 75 80 85 90 95 100 105 110 115 vi rf1 , vi rf2 ( db v ) 94 9427 vo ( db v ) 30 c 30 c 90 c if third order interference characteristic of the interfer- ence sensor (mixer) 20 30 40 50 60 70 80 90 100 70 75 80 85 90 95 100 105 110 115 vi rf ( db v ) 94 9428 vo ( db v ) 30 c 30 c 90 c if conversion characteristic of the interference sensor (mixer) interference sensor (amplifier) 1 5 6 2 50 t amb il1 1 : 2 f if r g9 = 200 vi if9 9 10 v s i10 if il1=0.7db 2vi if 94 9429
u4065b rev. a4, 06-mar-01 18 (23) agc thresholds 41.0 41.5 42.0 42.5 43.0 43.5 44.0 44.5 45.0 3020100 102030405060708090 t amb ( c ) 94 9430 threshold ( db v ) agc threshold of the interference if amplifier versus temperature 80 82 84 86 88 90 92 94 96 98 100 3020100 102030405060708090 t amb ( c ) 94 9432 vi 15/16 rf u13 = 0 v i13 = 30 a i13 = 0 a wideband agc threshold (i 10 = 1 a) versus temperature 85 90 95 100 105 0 5 10 15 20 25 30 35 40 45 50 55 i 13 ( a ) 94 9433 vi ( db v ) rf 88 mhz 98 mhz 108 mhz wideband agc threshold (i 10 = 1 a) versus i 13
u4065b rev. a4, 06-mar-01 19 (23) agc characteristics 0.01 0.10 1.00 10.00 100.00 1000.00 10000.00 35 45 55 65 75 85 95 vi if ( db v ) 94 9431 30 c 30 c 90 c i ( a ) 10 agc characteristic of the interference if & detector block 0.01 0.10 1.00 10.00 100.00 1000.00 10000.00 90 95 100 105 110 115 120 vi rf ( db v ) 94 9434 i ( a ) 30 c 30 c 90 c 10 characteristic of the wideband agc (v13 = 0 v) 0.01 0.10 1.00 10.00 100.00 1000.00 10000.00 80 85 90 95 100 105 110 115 120 vi rf ( db v ) 94 9435 i ( a ) 30 c 30 c 90 c 10 characteristic of the wideband agc (i13 = 0 v)
u4065b rev. a4, 06-mar-01 20 (23) dc characteristics 0 2 4 6 8 10 12 14 16 18 6.0 6.5 7.0 7.5 8.0 8.5 9.0 9.5 10.0 v s ( v ) 94 9436 i ( ma ) i3 i6 i18, i19 supply currents versus supply voltage 0 5 10 15 20 25 30 35 40 30 10 10 30 50 70 90 t amb ( c ) 94 9437 i ( ma ) i18, i19 i3 i6 i3 + i6 + i18 + i19 supply currents versus temperature 3.81 3.82 3.83 3.84 3.85 3.86 3.87 3.88 3020100 102030405060708090 t amb ( c ) 94 9438 v ( v ) ref reference voltage versus temperature 3.75 3.80 3.85 3.90 3.95 4.00 10 8 6 4 2 0 2 i 17 ( ma ) 94 9439 v ( v ) ref reference voltage versus i 17
u4065b rev. a4, 06-mar-01 21 (23) (tracking adj.) r10 1.5k r4 470 c7 1n appr. 8ma r7 56k c12 18p r13 120k r16 15 r19 10k c21 1n l6 osc l5 if cf3 r17 470 d5 c18 100p r14 160k d4 c13 1n r11 56k c8 10p r6 47k l2 2.2uh r5 22 c10 1p5 q1 l4 c14 1n c16 6.8p c17 150n c20 22p c22 6.8p c23 47p 1 24 u4065b 12 13 c11 10n d3 l3 r1 22 r2 100 d2 s391d r3 56k c5 10n c1 2p7 d1 s392d c2 1n c3 10n c4 1n q2 bc858 cf1 cf2 c19 22n r18 330 r20 22k r21 100k gain adj. c24 1n cf4 r15 22 r9 220 r12 330k c15 100n c9 470n c6 1n l1 220nh c25 27p 75 ohm ant vagc vtun 1.76.5v vs=8.5v if out lo out 1 3 4 6 bfr93a 1 2 3 4 6 820 c26 4.7p 94 9440 application diagram
u4065b rev. a4, 06-mar-01 22 (23) part list item description q1 bfr93ar (bfr93a) q2 bc858 d1 s392d d2 s391d d3, 4, 5 bb804 l1 11 turns, 0.35 mm wire, 3 mm diameter (approx. 220 nh) l2 2.2 h (high q type) l3 toko 7kltype # 600enf-7251x item description l4 toko 7kltype # 291ens 2341ib l5 toko 7kltype # m600bcs-1397n l6 toko 7kltype # 291ens 2054ib cf1 toko type skm 2 (230 khz) cf2, 3, 4 toko type skm 3 (180 khz) ordering and package information extended type number package remarks u4065b-afl so 24 plastic U4065B-AFLG3 so 24 plastic taping according ice-286-3 package information 13037 technical drawings according to din specifications package so24 dimensions in mm 15.55 15.30 2.35 0.4 1.27 13.97 9.15 8.65 0.25 0.10 7.5 7.3 0.25 10.50 10.20 24 13 112
u4065b rev. a4, 06-mar-01 23 (23) ozone depleting substances policy statement it is the policy of atmel germany gmbh to 1. meet all present and future national and international statutory requirements. 2. regularly and continuously improve the performance of our products, processes, distribution and operating systems with respect to their impact on the health and safety of our employees and the public, as well as their impact on the environment. it is particular concern to control or eliminate releases of those substances into the atmosphere which are known as ozone depleting substances (odss). the montreal protocol ( 1987) and its london amendments ( 1990) intend to severely restrict the use of odss and forbid their use within the next ten years. various national and international initiatives are pressing for an earlier ban on these substances. atmel germany gmbh has been able to use its policy of continuous improvements to eliminate the use of odss listed in the following documents. 1. annex a, b and list of transitional substances of the montreal protocol and the london amendments respectively 2. class i and ii ozone depleting substances in the clean air act amendments of 1990 by the environmental protection agency (epa) in the usa 3. council decision 88/540/eec and 91/690/eec annex a, b and c (transitional substances) respectively. atmel germany gmbh can certify that our semiconductors are not manufactured with ozone depleting substances and do not contain such substances. we reserve the right to make changes to improve technical design and may do so without further notice . parameters can vary in different applications. all operating parameters must be validated for each customer application by the customer. should the buyer use atmel wireless & microcontrollers products for any unintended or unauthorized application, the buyer shall indemnify atmel wireless & microcontrollers against all claims, costs, damages, and expenses, arising out of, directly or indirectly, any claim of personal damage, injury or death associated with such unintended or unauthorized use. data sheets can also be retrieved from the internet: http://www.atmelwm.com atmel germany gmbh, p.o.b. 3535, d-74025 heilbronn, germany telephone: 49 (0)7131 67 2594, fax number: 49 (0)7131 67 2423

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