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in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 1 / 16 ? ? r r e e v v i i s s i i o o n n 1 1 0 0 - - introduction description the in-plug ? ips15h is an enhanced off-line switcher version of the ips15 that includes the same basic features plus offers a special overload protection mode called hiccup to control the maximum output power from the line side and eliminate the current sensing circuitry on the load side. the original functions of the ips15 have been retained. they include soft start, line over-voltage protection, shunt-regulator , precision oscillator, pwm with its associated comparator and loop compensation components as well as all the necessary biasing and protection circuitry (thermal shutdown, under-voltage, over-voltage and over-current). the ips15h hiccup circuitry involves a counter and some other digital blocks. this feature has been added to avoid delivering a high current to the load in an overload condition, which may result in damages to the smps, the load or both . the overload condition is sensed from the line-side by monitoring the mosfet current. the mosfet must be allowed to operate at maximum current for the smps to properly start and respond to transient conditions. if the operation at maximum current is too long, then it is in an overload condition and the circuit enters "hiccup mode". the peak current in the load is still high in order to be able to return to normal mode, but the duty cycle is so low that the average current drops below 100ma therefore allowing the smps to remain overloaded indefin itely without any reliability or safety concerns. the ips15h not only protects against overload conditions but also avoid the losses involved in the sensing circuitry which increases the overall smps efficiency by up to 10%. this is significant! features ? hiccup version of the ips15 with overload protection. ? max output power controlled from line-side to avoid load-side current sensing circuitry and associated 10% losses. ? fail-safe protection from optocoupler failure when combined with low-cost low-power zener. ? lower quiescent current (max. 50% of the ips15) ? can drive a large variety of power mosfets ? simple, less critical, lower cost transformer. ? wide range pwm for stable operation at any load and line voltage. ? operates with optocoupler or bias winding for constant voltage applications: zeners, adjustable shunt regulator like tl431. ? emi reduction in critical applications thanks to: ? adjustable operating frequency. ? separate mosfet n & p drives ? power shut-down for stand-by modes. ? cycle to cycle over-current protection ? under-voltage lock-out ? line over-voltage protection. ? external component savings: mov, x-cap, y-cap (application permitting) applications ? standby power supplies for tv, vcr and ir remotely-controlled appliances. ? cordless and feature phones. ? cellular phone chargers. ? power tools fast chargers with trickle and on/off. ? laptops and personal digital assistants. ? utility meters. ? replacements for bulky plug-in transformers. in-plug ? series: i i p p s s 1 1 5 5 h h enhanced off-line s s w w i i t t c c h h e e r r w w i i t t h h h h i i c c c c u u p p , , low cost, high efficien cy, low stand-by power. f f a a i i l l - - s s a a f f e e protection from optocoupler failure when combined with low power zener. downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 2 / 16 pin configuration: dip-8 / soic-8 ordering information functional block diagram typical application sc hematic: ac in 90-265v, dc out 5v, imax 600ma figure 1 note: original r2 has been split into r2 and r2a to double the voltage rating. pdrive ndrive isense vcc rbias overv opto gnd ips15h 1 45 8 part no. rohs / pb-free package temperature range ips15hc-d -g-lf 8-pin pdip 0 c to +70 c commercial ips15hi-d -g-lf 8-pin pdip -40 c to +85 c industrial ips15hc-so -g-lf 8-pin soic 0 c to +70 c commercial ips15hi-so -g-lf 8-pin soic -40 c to +85 c industrial for detailed orderin g information , see p a g e 15 ref2 bandgap reference _ _ + + r q s rbias gnd ndrive overv isense opto vcc under voltage lockout thermal shutdown enb pwm comparators current limiting oscillator shunt regulator filters ref3 over v oltage lockout enb ref1 soft start pdrive v cc gnd 5v sw ips15h sw hiccup control v cc q1 nmosfet 1a, 600v u2 opto q817c r14 4.7k d2 d3 2 x 1n4148 r4 2.2 sm t r3 1k 1/2w c4 120pf 600v r5 330k smt 3 1 4 2 br1 br idge out+ ou t- secondar ygnd pr imarygnd r2a 430k sm t 90v-270v ac snubber network patented tx1 ei/ ee ferrite noise- canceling type lp=1.5mh ls=1.5micr oh + c6 470uf 16v + c3 10uf16v + c1 4.7uf 400v d3 schottky 1a - 60v l1 330uh + c2 4.7uf 400v r2 390k smt r10 4.3k smt r10a 1.5k smt r11 100k smt r12 10meg 1/4w c1 220pf smt ref 1 k 3 a 2 u3 tl431 r15 10k r16 10k output c7 r17 loop compensation pdrv 1 isense 2 vcc 3 rbias 4 ndrv 8 gnd 7 opto 6 ovrv 5 u4 ips15h r15 and r16 t o be adjusted according to output v oltage input r4 controls max pick current when the isense pin v oltage exceeds ~700 mv r11 and r12 to be adjusted f or max line ov erv oltage protection downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 3 / 16 hiccup mode: the output power that triggers the hiccup mode is m onitored from the line-side by sensing the mosfet current through the isense resistor (r4 in the example of fi g.1). the hiccup mode doesnt require any specific component on the load-side. this mode called hiccup is a special overload protection mode where the ips15h resets itself when an overload condition is detected and wh ich duration exceeds the maximum authorized time t hdtc as described below: approximatly t hoff after power-up and when the ips15h is fully operational, the output power is sensed to check an overload condition present or not (true or false) . if it is true and remains true all over t hdtc then the ips15h resets. power supply re-establishes and after t hoff time, the chip restarts monotoring the output power through rsense and the hiccup mode could repeat itself as described. if the overload condition is false or when it is true for less than t hdtc , the ips15h simply operates like the original ips10 / ips15 flyback controllers. overload condition: an overload condition is defined by p sout > p smax ? true; p sout < p smax ? false; p sout = smps output power (secondary); p smax = maximum authorized output power delivered by the smps secondary. hiccup detect time t hdtc and off time t hoff : t hoff = time from start-up to p sout sensing; t hdtc = maximum detect time of overload condition to trigger chip reset; (t hoff + t hdt c )/ t hoff. = hiccup duty cycle. calculation of the output power p smax that triggers the hiccup mode: as explained above, when p sout > p smax for more than t hdtc time, hiccup mode starts. the previous formula could also be seen from the primary as p sout = (p pout - losses) > p smax where losses correspond to the overall losses (schottky, transformer, mosfet, snubber etc..). as a first approximation the lo sses could be estimated to 25% and consequently 75% of primary power p pmax could be used. p pout > (p smax + losses) = ? l p ipeak 2 f ? ipeak = 0.7v/rsense (0.7v = max isense pin voltage, ipeak = peak mosfet current). p smax /0.75 = ? l p ipeak 2 f = ? l p (0.7v/rsense) 2 f this relation will help the smps designer to determine the 3 suitable parameters for their application: lp = primary inductance of tx transformer, rsense = isense resistor, f = frequency of operation. as in our example of fig.1 with r4 = 2.2ohm, l p =1.5mh and f= 70khz ? pout = 4w C losses ~ 3w. at 5v, the overload condition is set true when ipeak reaches approximatly 600ma. calculation of hiccup detect time (t hdtc ) and off time (t hoff ) t hdtc is proportional to 1/f and typically is 7ms for f nom =70khz. to calculate t hdtc at any other frequency, apply 7ms x f nom /f1. example: f1= 50khz, t dtc = 7ms x 70khz/50khz ~ 10ms t hoff ~ 6 x (r2 +r2a) x c3 . in the exampl e of figure 1, with vin =90v, t hoff ~ 6 x 1.5m x 10 f ~ 1s vin rms 90v figure 2: ?hiccup? mode in constant overload note: conditions of figure 2 were altered to better show the hiccup operation mode. actual duty cycle will be much less as indicated in formula below. downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 4 / 16 calculation of the max value of the output capacito r c6 (see fig. 1): during the power-up phase, the output capacitor c6 needs to be fully charged within the hiccup detect time t hdtc otherwise the ips15h would detect an overload conditi on which doesnt exist and will enter hiccup mode. please calculate the maximum capacitor value suitable for your application by applying: c6 max lp x 385 x (ipeak) 2 where lp = primary inductance of tx transformer vout 2 ipeak = maximum peak current in the mosfet vout = output dc voltage of the smps in the schematic page 2, the calculation of c6 max shows an absolute max value of ~ 2300 f. protection against optocoupler failure using a simp le low-cost, low-power zener figure 3 when adding a zener diode with a voltage slightly a bove the maximum output dc operating voltage, the smps will automatically enter hiccup mode if the optocoupler fails open. thanks to entering hiccup mode, the average power dissipa tion in the diode will be limited to a small fraction of what the smps could deliver when the f eedback loop is opened. this is why a low-power zener is sufficient for full protection. therefore the combination of the ips15h hiccup capability with a simple low-power low-cost ouput diode brings a very affordable protection against optocoupler failure, av oiding destruction of the load and the smps itself. a simple replacement of the optocoupler then will bring the smps back to normal operation. as already described in the front page, in hiccup mode the average current drops well below 100ma. a very low- power rated zener can be therefore selected according to th e intrinsic voltage required by the application. this will allow the smps to remain overloaded indefinite ly without any reliability or safety concerns. q1 nmosfet 1a, 600v u2 opto q817c r14 4.7k r4 2.2 smt r5 330k smt out+ out- secondar ygnd pr imar ygnd tx1 ei/ ee ferrite noi se- cancel ing type lp=1.5mh ls=1.5mi cr oh + c6 470uf16v d3 schottky 1a - 60v r10 4.3k smt r10a 1.5k smt r11 100k smt r12 10meg 1/4w c1 220pf smt ref 1 k 3 a 2 u3 tl431 r15 10k r16 10k zener c7 r17 loop compensat ion pdrv 1 isense 2 vcc 3 rbias 4 ndrv 8 gnd 7 opto 6 ovrv 5 u4 ips15h dc in vcc in z1 required protecti on fail-safe from one low-power optocoupler failure downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 5 / 16 in-plug ? ips15h functional description as the ips15, the in-plug ? ips15h is a pwm controller for flyback switching power supply applications. this version has been designed to protect smpss from overlo ad conditions with a minimum circuitry and minimum load side losses. the principal features are: - low quiescent current (half of ips15); - max output power (overload) controlled from line-side; - shunt regulator to allow the maxi mum flexibility to power the chip; - protections against overheating, and line over-voltage; - under-voltage lockout; - precise oscillator with externally adjustable frequency; - on-chip filters for the loop compensation and the over-current sensing; - soft start and over-voltage s hut-down to protect the mosfet; - separate mosfet p and n drivers to adjust rising and falling edge independently. the shunt regulator operates like a zener diode, keeping the chip supply voltage around 9.7 volts. at start-up the chip stays in stand-by mode until the voltage of vcc reach es about 9.7 volts. during this phase, the consumption is of the order of 60 a and the ic being partially disabled can onl y handle a maximum of 1ma of supply current. when the 9.7 volts are reached, the driver starts providing gate pulses. the chip will go back to the stand-by mode if the supply voltage decreases down to ~8 volts. the over all chip consumption in normal operation is about 350 a, not counting the current required to drive the mosfet gate. for domestic application, the chip can be supplied from the r ectified line voltage through a resistor. in such case, the resistor has to be sized to drive enough current to the chip. for international applications, the ic gets the start curre nt from a resistor connected to the rectified line voltage (~70 a) then, after the first gate pulse, the patented modified snubber network (*) provides the additional current to keep the chip running. the opto pin is pulled to internal 5v through an on-chip resistor which value is 60k nominal, allowing a maximal duty cycle of 66 %. during start-up, the duty cycle is controlled by the internal soft start unit which smoothly increases the mosfet current up to its maximum, corresponding to 700mv developped across the sense resistor. when the expected output voltage is reached, the optocoupl er's led is driven, and the opto pin voltage decreases, reducing the duty cycle to a controlled value. the initial cu rrent limiting protection of the original ips15 that was simply turning-off the mosfet when the isense pi n voltage exceeds ~700 mv, is now used to trigger the hiccup mode when the condition is present for a maximum time defined by an internal ips15h digital counter. pin description number name description 1 pdrive internal p drive terminal to be connected to the gate of the outside power mosfet. (the rising edge can be ad justed with an external resistor) 2 i sense mosfet current sensing. any voltage over 700 mv @ 25c on this pin for an internally defined number of clock cycles, will trigger hiccup mode. 3 v cc ic positive supply. the chip behaves like a 9.7 volts zener diode. 4 r bias external r bias connection to set the operating frequency. 5 overv line over-voltage lock-out pin. @ 25c a voltage over 4v on this pin will pull the mosfet gate to gnd. 6o p t o feedback input 7g n d ground 8 ndrive internal n drive terminal to be connected to the gate of the outside power mosfet. (the falling edge can be adjusted with an external resistor) downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 6 / 16 this overload condition is sensed from the line-side by monitoring the mosfet current. the mosfet must be allowed to operate at maximum current for the smps to properly start and respond to transient conditions. when the time of operation at maximum current counter overfl ows, it is in an overload condition and the circuit enters "hiccup mode". the peak current in the load is still high in order to be able to return to normal mode, but the duty cycle is so low that the average current drops below 100ma therefore allowing the smps to remain overloaded indefinitely without any reliability or safety concerns. the line-side voltage limiting protection operates by turning-off the mosfet wh en the overv pin voltage exceeds ~4v.(*) us patent # 6,233,165 - royalty free licence for in-plug ? customers. ac 110v - ips15h normal operation at 5w * ips15h normal operation at 15w* ac 250v - ips15h normal operation at 5w* ips15h normal operation at 15w* ** together with a 1a, 600v mosfet. vout drain isense vout isense drain vout isense drain vout isense drain downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 7 / 16 output power capability part number package 230v ac or 115v ac w/ doubler 85 ? 285v ac ips15h dip-8 / soic-8 up to 70w (1) up to 30w (1) note (1): governed by size and package of external mosfet electrical characteristics absolute maximum rating characteristics value units shunt regulator max i cc in normal operation (pin 3) - see fig 6- 50 ma shunt regulator max i cc at start-up 1 ma all analog inputs (pin 2, 4, 5, 6) min= -0.3, max= +6.3v v peak drive output current (pin1) source=100, sink=170 ma junction to case thermal resistance r j-c pdil = 42, soic = 45 junction to pcb thermal resistance r j-a pdil = 125, soic =155 c / w power dissipation for t a <= 70c pdil = 640, soic = 500 mw operating junction temperature - 40 to 150 storage temperature range - 55 to 150 lead temperature (3 mm from case for 5 sec.) 260 c parameter test conditions parameters units @ 25c unless specified min. typ. max. supply, bias & circuit protection shunt regulator voltage icc = 1 to 30 ma 9.2 9.7 10.5 v shunt regulator dynamic resistance 1 to 30 ma 2 3 5 shunt regulator max peak repetitive current -3 5- m a min i cc to start oscillator - - 80 under voltage lock-out v cc ? 2.2 v cc - 1.5 v cc - 1.4 v min i cc to ensure continuous operation 1a, 600v, 5 nc mosfet 1.1 @ 20khz 3.2 @ 80khz 4.9 @ 150khz ma current limiting sensing voltage 655 700 745 mv temperature coefficient of current limiting -3 0- v/c overvoltage sensing voltage 3.85 4 4.15 v soft/start duration 0 to 700mv - 30 - clock cycles leading edge blanking - 900 - ns thermal shutdown trip temperature - 140 - c downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 8 / 16 electrical characteristics (cont d) parameter parameter parameters units @ 25c unless specified min. typ. max. oscillator & pwm range of operating frequencies 30 80 150 khz rbias values for above frequencies (see figure 4) 550 170 80 k oscillator stability with supply & temperature (see figure 5 for average) i cc = 5 ma temp = 0 to 70c -1.5 - 1.5 % maximum duty cycle - 66 - % minimum duty cycle - 0 - % hiccup run time t hdtc f = 70 khz* - see note2 - 7 - ms hiccup off time t hroff proportional to r2 x c3 see explanation page 3 error amplifier sensitivity in mv / % of pwm - 54 95 mv voltage for max duty cycle (on opto pin) - 4 - v voltage for min duty cycle (on opto pin) - 0.6 - v input impedance opto pin 40 60 80 k p & n outputs to mosfet gate p gate driver saturation 10 ma (source) - - 1 v n gate driver saturation 10 ma (sink) - - 0.6 v gate pull-down resistor (internal) 280 400 520 k pdrive rise time (10% to 90%) 240 pf load - 150 - ns ndrive fall time (10% to 90%) 240 pf load - 75 - ns max recommended total external mosfet charge @ 20 khz - - 100 nc ? @ 80 khz - - 50 nc ? @ 150 khz - - 15 nc note1: electrical parameters , although guaranteed, are not a ll 100% tested in production. * note2: detect time t hdtc is proportional to 1/ f. for example at 50khz, detect time t hdtc = 7ms x 70khz / 50khz = 10ms (full explanation page 3) downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 9 / 16 figure 4: frequency vs rbias 10 30 50 70 90 110 130 150 170 190 0 50 100 150 200 250 300 350 400 450 500 550 rbias (k ohm) frequency (khz) figure 5 frequency drift vs temperature -2.00 -1.00 0.00 1.00 2.00 - 2 0- 1 0 0 1 02 03 04 05 06 07 08 09 01 0 0 temperature (c) frequency variation (%) icc=5ma downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 10 / 16 * note: do not attempt to force more than 1ma into vcc pin during start-up. good design practices ips15h and loop stability: the ips15h is intrinsically very fast and doesnt participate to the loop stability. it only involves a comparator that doesnt bring any gain and exhibits a negligible phase shift. it has been designed on purpose to allow its utilization in a large range of applications: (a) operating at frequencies up to 200 khz and even above, (b) involving very different types of loop stability from "cyc le skipping" where the loop is not compensated at all, to good stability achieved through the utilization of a tl431 and finally superior transient response when using half of the ips25 feedback controller. the loop compensation is entirely achieved on the load side and the feedback is performed by an optocoupler which gain and dynamic response play an important role in the loop stability. precaution in selecting the optocoupler: the optocoupler must be using a phototransistor and not a photodarlington. most optocouplers of this type are offered in a wide range of coupling efficiency, also calle d transfer ratio. even the cheapest ones have a guaranteed transfer ratio of the order of 100% meaning that 1ma of current in the ir led creates approximately 1ma of current in the receiving phototransistor. the user should be able to design the loop to be stable even though the actual transfer ratio differs by more than a factor of 3 (example from 100% to 300% or 50% to 150%). unfortunately optocouplers were not designed for low-current applications and this results in very bad speed and saturation characteristics for the phototransistor which coul d become incredibly slow and create severe loop stability problems should it be allowed to saturate hard in the application (the optocoupler coul d cause the ips15h to skip cycles due to the long time required by the opto transistor to go out of saturation). figure 6: shunt regulator v/i characteristics* 0 10 20 30 40 50 024681 01 21 4 vcc (v) icc (ma)- downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 11 / 16 in the example of figure 1, the output voltage is 10 volts as defined by r15 and r16 and 2.5v at the pin #1 of the t l431. the cathode of the tl431 can go to a voltage as low as 2 volts. the ir led requires approximately 1 volt which mean s that the voltage drop across r14 could be up to 6 volts resulting in a maximum current of 700ua. this value is plentiful for the utiliza tion of a broad range of optocouplers and yet small enough to avoid hard saturation. loop stability with the tl431: the tl431 has an enormous dc gain and will not ensu re stability unless specific loop-compensation components such as a rc network are added as indicated below. the rc network should have a cut-off frequency at 100h z to roll-off the gain at low frequencies but reach a plateau around 100hz and have enough ac gain at twice the line frequency and achieve a good line ripple rejection. this is achieved by the loop compensation network c7, r17 of figure1. the gain rolls off until the impedance of c7 reaches the value of r7. at much higher frequencies, th e gain continue to roll-off due to the natural frequency response of the tl431. the goal is to reach a very low gain at the switching frequency. if the addition of c7 & r17 with valu es as shown results in gain is too low, the values of r15 & r16 should be reduced in proportion to lower the impedance at pin #1 of tl 431. alternately, if the gain is too high the values of r17 should be reduced and c7 re-adjusted accordin gly to maintain the required cut-off frequency. criteria to calculate the network : 1) r17 must be much higher than the input resistance of tl431 constituted by r16//r15=5k ? 68kohm ok. 2) f=100hz=1/(2 x 3.14 x r17 x c7) gives approximately 22,000 pf for c7. discontinuous operation: check discontinuous mode of operation of the transformer (see application note an-ips02 page 2 for details) to ensure that the flyback smps is indeed operating in discontinuous mode in the entire range of input voltages and output current. the response of th e smps drastically changes in continuous mode, it gets considerably slower which requires a totally different loop compensation techni que. remember that it is very difficult to ensure loop stability with a simple schematic when the smps is allowed to transition between discontinuous and continuous modes. mosfet driver protection: the mosfet driver has been sized to be capable of dr iving power mosfets featuring a total gate charge up to 100nc. the mosfet should be turned-on relatively slowly and turned-off much faster. these 2 parameters can be independently adjusted through the external resistors r10 (pin1) and r10a (pin8). the minimum value of these resistors should be 50 in order to reduce emi and minimize the noise injection which could result from miller-capacitance kick-back during transient conditions. see application note an-ips-02 for emi reduction techniques. downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 12 / 16 additional recommendations: for best results in low power off-line smpss with the ips15h , the following mosfet features are recommended: - low gate charge (max 50 nc). - 400 v breakdown voltage for domestic use (usa / japan). - 600v breakdown voltage for european use (800v when transformer leakage inductance is very small). - 1, 2 or 3a depending on the maximum output power. examples of suitable mosfets: - ixys polarht ? and polar hv ? mosfet series: ixty1r4n 60p, ixty2n60p, ixty3n60p - fairchild mosfet series: fqpf1n60, fqpf 2n60, fqpf 3n60. - infineon coolmos tm series: spd01n60s5, spd02n60s5, spd03n60s5. - motorola mosfet series: mtp1n60, mtp2n60, mtp3n60. - sgs-thomson mosfet series: std1nb60, std2nb60, std3nb60. - etc? notes: - due to the rapid evolution of mosfe t technologies, please check for current models when designing a new smps. - polarht ? and polar hv ? are trademarks of ixys corporation - coolmos tm is a trademark of infineon. - transformer characteristics : (a) transformer design: e-core with suitable gap to prevent saturation or distri buted-gap toroid. primary inductance of 1.5 mh is very typical in 5 -10w appli cations with 5v output dc: turn ratio = 9 for 220v input or universal 85v C 265v. turn ratio = 7 for 100-120v ac input (japan and usa) (b) transformer phasing: check the phase indicated in figure 1. also re fer to applications notes an-ips-01 and an-ips-02. snubber network : with reference to figure 1, r2 + r2a provide the start-up current for the chip. c3 is being charged through r2+r2a. once the chip supply voltage is high enough, the ga te drive starts and the chip is then powered by the modified snubber network presently being patented by our company. the snubber values may have to be optimized for different specific operating conditions: - r3 could be reduced to 100 ohms and sometimes eliminated. - c4 could be increased to 200pf and sometimes more. depending on the characteristics of the transformer, essen tially leakage inductance and distributed capacitance, the snubber network shown in figure 1, may not be efficient enough to reduce the voltage spikes when operating at 20w or above. please refer to applicati ons notes an-ips-01 and an-ips-02 design tips or emi reduction techniques, or feel free to contact our t echnical support for assistance. downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 13 / 16 power shut-down solutions for stand-by requirements : for low-power stand-by requirements, the primary circ uitry can be shut-down by pulling the ips15h vcc pin low through a 100 resistor. this can be easily done using a: simple switch pnp transistor npn transistor figure 7 solution 1: simple switch, close = off 100 resistor mandatory solution 2: pnp transistor, low = off (low = less than 4v) 100 resistor optional solution 3: npn transistor, high = off 100 resistor optional close = off 100 100 low = off high = off 100 when the "low" state is released, the vcc is naturally re-established, re-activating the ips15h. q1 nmosfet 1a, 600v u2 opto q817c r14 4.7k d2 d3 2 x 1n4148 r4 2.2 smt r3 1k 1/2w c4 120pf600v r5 330k smt 3 1 4 2 br1 bridge out+ out- secondarygnd primarygnd r2a 750k smt 90v-270v ac snubber network patented tx1 ei/ee ferrite noise- canceling type lp=1.5mh ls=1.5micr oh + c6 470uf16v + c3 10uf16v + c1 4.7uf 400v d3 schottky 1a - 60v l1 330uh + c2 4.7uf 400v r2 750k smt r10 4.3k smt r10a 1.5k smt r11 100k smt r12 10m eg 1/4w c1 220pf smt ref 1 k 3 a 2 u3 tl431 r15 10k r16 10k output c7 r17 loop compensation pdrv 1 isense 2 vcc 3 rbias 4 ndrv 8 gnd 7 opto 6 ovrv 5 u4 ips15h input shut-down solutions 1,2 or 3 downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 14 / 16 package dimensions plastic dip-8 plastic soic-8 downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 15 / 16 ordering information part-number example of marking (note : for production with a new date code, since j anuary 2006, the package type does not appear anymore on package marking) this ordering information is for commercial and industrial st andard in-plug ? controllers only. for cu stom controllers or for automotive and m ilitary temperature ranges, call aai?s sales representative. in-plug ? controller series flyback feedback pfc push-pull led driver controller type flyback: 10 series feedback: 20 series pfc: 100 series push-pull: 200 series led driver: 400 series ?h? with hiccup overload protection rohs + pb-free tape and reel tr : tape & reel tu : tube note1 : default or not specified is ? tube ?. note2 : does not appear on package marking. temperature range c : commercial (0, +70c) i : industrial (-40c. +85c) note : default or not specified is package type d : dip8 so : soic8 (for production with a new date code, after january 2006, the package type will not appear anymore on package marking) ips xxxh c C yy C g-lf - tr non-green package green rohs + pb-free package aai g-lf ips15hc yyww aai ips15hc yyww downloaded from: http:///
in-plug ? i i p p s s 1 1 5 5 h h datasheet C rev. 10 C hiccup flyback c c o o n n t t r r o o l l l l e e r r C C e e a a s s y y o o p p t t o o f f a a i i l l s s a a f f e e p p r r o o t t e e c c t t i i o o n n ? copyright 2003-2007 - asic advant age, inc. C all ri ght s reserved - revision 10 C april 02, 20 07 16 / 16 the following is a brief overview of certain terms and conditions of sale of pro duct. for a full and complete copy of all the general terms and conditions of sale, visit our webpage ht tp://www.asicadvantage.com/terms.htm. limited warranty the product is warranted that it will conform to the applicable specifications and be free of defects for one year. buyer is responsible for selection of, use of and results obtained from use of the product. buyer indemnifies and holds asic advantage, inc. harmless for claims arising out of the application of asic advantage, inc.?s products to buyer?s designs. applications described herein or in any catalogs, advertisements or other documents are for illustrative purposes only. critical applications products are not authorized for use in critical applications including aerospace and life support applications. use of products in these applications is fully at the risk of the buyer. critical applications include any system or device whose failure to perform can result in significant injury to the user. lethal voltages lethal voltages could be present in the applications. pl ease comply with all applicable safety regulations. intellectual property rights and proprietary data asic advantage, inc. retains all intellectual property rights in the products. sale of products does not confer on buyer any license to the intellectual property. asic advantage, inc. reserves the right to make changes without notice to the products at any time. buyer agrees not to use or disclose asic advantage inc.?s proprietary information without written consent. trademarks and patents - in-plug ? is a registered trademark of asic advantage, inc. - aai?s modified snubber network is patented under the us patent # 6,233,165. in-plug ? customers are granted a royalty-free licence for its utilization, provision the parts are purchased factory direct or from an authorized agent. protection for custom in-plug ? solutions when aai accepts to design and manufacture in-plug ? products to buyer?s designs or specifications, buyer has certain obligations to provide defense in a suit or proc eeding claiming infringement of a patent, copyright or trademark or for misappropriation of use of any trade secrets or for unfair competition. compliance with laws buyer agrees that at all times it will comply with all applicable federal, state, municipal, and local laws, orders and regulations. buyer agrees to comply with all applicable restrictions on exports and re-exports including obtaining any required u.s. government license, authorization, or approval. buyer shall pay any duties, levies, taxes, brokerage fees, or customs fees imposed on the products. title and delivery all shipments of goods shall be delivered exworks, sunnyvale, ca, u.s.a. title in the goods shall not pass to buyer until asic advantage, inc. has received in full all amounts owed by buyer. latest datasheet updates for the latest datasheet updates, visit our web page: http://www.in-plug.com/datasheets.htm. worldwide representatives to access aai?s list of worldwide representatives , vi sit our web page http://www.in-plug.com/representatives.htm copyrights copyrights and all other proprietary rights in the content re sts with asic advantage inc. (aai) or its licensors. all rights in the content not expressly granted herein are reserved. except as otherwise provided, the content published on this document may be reproduced or distributed in unmodified form for personal non-commercial use only. any other use of the content, including without limitation distri bution, reproduction, modification, display or transmission without the prior written consent of aai is strictly prohibited. all copyright and other proprietary notices shall be retained on all reproductions. asic advantage inc . 1290-b reamwood ave, sunnyvale california 94089, usa tel: (1) 408-541-8686 fax: (1) 408-541-8675 websites: http://www.in-plug.com - http://www.asicadvantage.com downloaded from: http:///

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